base band transmission
TRANSCRIPT
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[ ]
(4.7))(2
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(4.6))(2
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(4.10))()(iffholds(4.9)inequalityThe
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Since g(t)
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[ ]
ratio)PSDnoiseenergy tosignal(waveformoftindependeniswhich
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Properties of Matched Filters
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2
Y
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(4.27))(
exp1
)0|(
isofpdflconditionaThe
(4.26)2
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1
(4.25))(2
),(
2PSDwithnoisewhiteis)(Since
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=
bb
Y
b
T T
b
Y
W
/TN
Ay
/TNyf
Y
TN
dt duutN
T
utN
utR
/Ntw
b b
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Figure 4.5 Noise analysis of PCM system. (a) Probabilitydensity function of random variable Yat matched filter output
when 0 is transmitted. (b) Probability density function of Y
when 1 is transmitted.
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+ = 00)(2
10 )exp(
1
/TN/A dzzP
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17Figure 4.6 Probability of error in a PCM receiver.
PCM receiver exhibits an exponential improvement in
with increase ineP 0/NEb
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4.4 Intersymbol Interference (ISI)
ISI arises when the channel is dispersive
Figure 4.7 Baseband binary data transmission system.
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(Polar form)
TX Filter Channel RX Filter
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Zero ISI
ionnormalizatby
,1)0(where =p
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kimkim
kim
==
=
if,0,if,0
Condition for zero ISI
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23W: Nyquist bandwidth
Ideal Nyquist channel
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Figure 4.8 (a) Ideal magnitude response. (b) Ideal basic pulse shape.
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Figure 4.9 A series of sinc pulses corresponding to the sequence 1011010.
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No margin of error in sampling times
0, =it
Caused by timing error
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Figure 4.10 Responses for different rolloff factors.
(a) Frequency response. (b) Time response.
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4.6 Correlative-level (Partial-response)
(Controlled ISI)Duobinary Signaling
Figure 4.11 Duobinary signaling scheme.
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Figure 4.12 Frequency response of the duobinary conversion filter. (a) Magnitude response. (b)
Phase response.
Figure 4.13 Impulse response of the duobinary conversion filter.
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Figure 4.14 A precoded duobinary scheme; details of the
duobinary coder are given in Figure 4.11.
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Figure 4.15 Detector for recovering original binary sequence from the precoded duobinary coder output.
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s
Figure 4.16 Modified duobinary signaling scheme.
Figure 4.17 Frequency response of the modified duobinary conversion filter. (a)
Magnitude response. (b) Phase response.
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Figure 4.18 Impulse response of the modified duobinary conversion filter.
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G li d F f C l ti l l di (PRS)
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Generalized Form of Correlative-level coding (PRS)
Figure 4.19 Generalized correlative coding scheme.
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43Figure 4.20 Output of a quaternary system. (a) Waveform. (b) Representation of
the 4 possible dibits, based on Gray encoding.
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Figure 4.24 (a) Near-end crosstalk (NEXT). (b) Far-end crosstalk (FEXT).
Figure 4.25 Model of twisted-pair channel.
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Figure 3.15 Line codes for the electrical representations of binary data.
(a) Unipolar NRZ signaling. (b) Polar NRZ signaling. (c)Unipolar RZ signaling.
(d) Bipolar RZ signaling. (e) Split-phase or Manchester code.
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Figure 4.18 Impulse response of the modified duobinary conversion filter.
Figure 4.20 Output of a quaternary system. (a) Waveform. (b) Representation of
the 4 possible dibits, based on Gray encoding.
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Figure 4.26 (a) Illustrating the different band allocations for an FDM-based ADSL
system. (b) Block diagram of splitter performing the function of multiplexer or
demultiplexer. Note: both filters in the splitter are bidirectional filters.
(DMT)
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Figure 4.7 Baseband binary data transmission system.
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Figure 4.29 Signal-flow graph representation of the LMS algorithm involving the kth tap weight.
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Figure 4.30 Illustrating the two operating modes of an adaptive equalizer: For the training
mode, the switch is in position 1; and for the tracking mode, it is moved to position 2.
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][][ knxkh
Figure 4.31 Impulse response of a discrete-time channel, depicting the precursors
and postcursors.
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Figure 4.32 Block diagram of decision-feedback equalizer.
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Eye Patterns
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y
Figure 4.33 Interpretation of the eye pattern.
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67Figure 4.34 (a) Eye diagram for noiseless quaternary system. (b) Eye diagram for quaternary system
with SNR = 20 dB. (c) Eye diagram for quaternary system with SNR = 10 dB.
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Figure 4.35 (a) Eye diagram for noiseless band-limited quaternary system:
cutoff frequencyfo = 0.975 Hz. (b) Eye diagram for noiseless band-limitedquaternary system: cutoff frequencyfo = 0.5 Hz.