isl6327eval5 user guide - renesas
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USER’S MANUAL
AN1268Rev 0.00
Oct 26, 2010
ISL6327EVAL5Voltage Regulator Coupled Inductor Solution using the ISL6327 and ISL6609
IntroductionToday’s microprocessors are continuing towards higher power consumption and functionality. Vcore regulators have the burden of increasing load demands coupled with tighter voltage regulation requirements. Power designers are challenged with the design of high performance regulators that can meet tight load regulation windows with increasing maximum load and transient requirements and falling output voltages. Add to that the push for higher efficiency solutions and decreasing PCB real estate; meeting today’s microprocessor power requirements is no simple task.
Intersil ISL6327 With Coupled InductorsTo help meet these design challenges Intersil offers a complete reference design and evaluation package that takes advantage of the features of the ISL6327 controller and an output filter topology using coupled inductors and fewer output capacitors.
The ISL6327 controls a microprocessor core voltage, balances channel currents, and provides protective features for up to 6 synchronous buck channels in parallel. The controller uses a 8-bit DAC giving the user a digital interface to select the output voltage, which is precisely regulated to ±0.5% accuracy using differential remote voltage sensing. The DAC can be set up to read VR10 or VR11 VID codes. Other features of the controller include overcurrent, overvoltage, and undervoltage protection, internal over temperature protection, programmable output voltage offset, dynamic VID circuitry, and an IOUT pin that provides a voltage proportional to the load current.
To meet the extremely fast load transients of microprocessors the ISL6327 utilizes Intersil’s proprietary Active Pulse Positioning (APATM) and Adaptive Phase Alignment (APATM) modulation scheme and continuous current sensing to achieve extremely fast load transient response with fewer output capacitors.
‘Coupled’ with the fast control scheme a new approach to the output filter can be implement using coupled inductors. Coupling of two phases on one core allows the use of a small output inductance for fast transient response without taking the hit in efficiency due to higher individual phase peak-to-peak current for an equivalent standard inductance.
The ISL6327 and ISL6609 datasheets along with the latest documentation can be found on our website: www.intersil.com.
ISL6327EVAL5 VRD Reference DesignThe evaluation kit consists of the ISL6327EVAL5 evaluation board, the ISL6327 datasheet, and this application note. The evaluation board is designed to meet the output voltage and current specifications shown in Table 1, with the VID DIP switches, SW2, set to 00101010 (1.35V).
The board is configured for down conversion from 12V to the DAC setting. The evaluation board provides many test points, two types of power supply connectors, an on-board LGA775/771 socket for transient response evaluation and terminal connectors for DC load testing. An on-board LED is present to indicate the status of the PGOOD signal.
The printed circuit board is implemented in 6-layer, 1-ounce copper. The layout and stackup are designed to emulate a real world CPU/VCORE implementation. The board schematic and BOM is provided at the end of the application note.
Quick Start EvaluationThe ISL6327EVAL5 is designed for quick start-up and evaluation. All that is required is a single ATX power supply. To begin evaluating the ISL6327EVAL5 follow the steps below.
1. Before doing anything to the evaluation board, make sure the “Enable” switch (EN1) is in the OFF position.
2. Using an ATX power supply, connect the 24-pin main power supply header to the “5V Power” connector (5V_PWR1) on the board. Next connect the 4-pin 12V header to the “12V Power” connector (12V_PWR1) on the board.
3. Set the “Static VID” DIP switch (SW2) to 00101010 (VID7:0 as printed on the silkscreen).Set SW1 to 0001.
4. Move the “Enable” switch (S1) to the ON position to begin regulation.
After step 4, the ISL6327EVAL5 should be regulating the output voltage. The test points “TPVCORE1” and “TPGND1” can be used to monitor the output voltage initially to verify regulation.
TABLE 1. ISL6327EVAL5 DESIGN PARAMETERS
PARAMETER MAX TYPICAL MIN
No Load VCORE Regulation 1.35V 1.33V 1.31V
VCORE Tolerance +20mV -20mV
Load Line Slope 1.25m
Continuous Load Current 130A
Load Current Step 100A
Load Current Transient 1200A/s
AN1268 Rev 0.00 Page 1 of 18Oct 26, 2010
ISL6327EVAL5
ISL6327EVAL5 Board Features
Input Power Connections
The ISL6327EVAL5 includes two different methods for powering up the board. The first method allows for the use of an ATX power supply. The 24-pin header, 5V_PWR1, allows for the connection of the main ATX power connector, while the 4-pin header, 12V_PWR1, connects the 12V AUX power. It is very important that both connections are secure and the EN1 switch is in the OFF position before switching on the ATX supply.
The second method of powering the ISL6327EVAL5 board is with bench power supplies. Four female banana jacks are provided for connecting bench-top supplies. A +5V, 1A and +12V, 20A supply will be needed for full evaluation. Connect the +5V terminal to the 5V1 jack and the +5V GND terminal to 5V_GND1. Connect the +12V terminal to 12V1 and the +12V GND terminal to 12V_GND1. Voltage sequencing is not required when powering the evaluation board.
Once power is applied to the board, the PGOOD LED indicator will illuminate red. With EN1 in the OFF position, the ENABLE input of the ISL6327 is held low and the start-up sequence is inhibited.
Output DC Power Connections
The ISL6327EVAL5 output can be exercised using a DC electronic load through the output terminal lugs labeled VCORE1 and GND1. Tie the positive load connection to VCORE1 and the negative load connection to GND1. A shielded scope probe test point, TP1, allows for inspection of the output voltage, VCORE. This probe is connected to VSENSE through 0 resistors on the back of the PCB labeled VTT_R1 and VTT_R2.
LGA775/771 VTT Evaluation
To fully exercise the regulation of the ISL6327EVAL5 a LGA775/771 VTT is needed. A LGA775/771 VTT socket is populated on the PCB. To ensure the ISL6327 regulates to the die sense location on the VTT, 0 resistors are populated on the back side of the PCB labeled R40 and R42. These must be populated for correct voltage measurements when using the VTT.
After inserting the interposer and VTT in the LGA775/771 socket a differential voltage probe should be connected to the VCC-REG-N/VSS-REG-N connector for voltage monitoring and the AMP and GND connector for load measurements.
For accurate measurements with the differential probes you must make sure that the ground terminal of your oscilloscope is connected to the ground plane of the ISL6327EVAL5. An easy way to do this is use a wire to connect the GND terminal of the scope to one of the GND test points on the ISL6327EVAL5 (TP10 for example).
The VTT must also be powered with +5V and +12V at the 4-pin power input connector. Refer to your VTT users guide and software for details on exact test setup and software use.
VID Setting
The VID input on the ISL6327EVAL5 can be set by using the on board SW2 DIP switch. The switches are labeled VID7 to VID0. Or the VID can be controlled through the VTT software. To select which method controls the VID pins of the ISL6327 the jumpers J_VID7 to J_VID0 need to be placed accordingly.
For VTT control of the VID, place the jumper hats on pins 1 and 2 of the 3-pin connector for J_VID7 - J_VID0. The 4th switch on SW1 should also be switched to VTT (labeled on the PCB silk-screen).
To allow the DIP switches to control the VID move switch 4 of SW1 DIP switch to DEMO and move the jumper hats to pins 2 and 3 of J_VID7 to JVID_0.
The VID DIP switches should be preset to 00101010 (1.35V with 20mV offset). If another output voltage level is desired, refer to the ISL6327 datasheet for the complete DAC table and change the VID switches accordingly.
Both VR10 and VR11 VID codes can be used with the ISL6327EVAL5. To use VR11 move switch 1 of SW1 DIP switch towards VR11. To use VR10 move switch 1 of SW1 towards VR10.
Enabling the Controller
In order to enable the controller, the board must be powered and a VID code must be set. If these steps have been properly followed, the regulator is enabled by toggling the “ENABLE” switch (EN1) to the ON position. When EN1 is switched, the voltage on the EN pin of the ISL6327 will rise above the ENLL threshold and the controller will begin the soft start sequence. The output voltage ramps up to the programmed VID setting, at which time the PGOOD indicator will switch from red to green.
Signal Test Points
There are many test points available on the ISL6327EVAL5 for monitoring of key signals. Monitoring test points include, VR_HOT and VR_RDY for monitoring the temperature FAULT outputs, OFS, IOUT, DAC, REF, COMP, EN, and DAC for monitoring control waveforms. There are also test points for monitoring VIN (VIN1 and VIN2) and VOUT (TPVCORE1 and TPGND1).
AN1268 Rev 0.00 Page 2 of 18Oct 26, 2010
ISL6327EVAL5
Component Selection With Coupled InductorsThere are many parameters of the operation of the ISL6327 that can be modified and tested using the ISL6327EVAL5 evaluation board. Many control signals can also be monitored through on-board test points. For detailed theory of operation and component selection guidelines for the ISL6327 please refer to the ISL6327 datasheet available on the web at www.intersil.com.
Key parameters that will be selected differently or otherwise impacted in the case where coupled inductors are used in the output filter are feedback compensation, DCR sense time constant, current sense resistor, droop control, and overcurrent set point. How to select these components will be covered in this section.
PWM Modulation Scheme and Continuous Current Sense
The ISL6327 adopts Intersil's proprietary Active Pulse Positioning (APP) modulation scheme to improve transient performance. APP control is a unique dual-edge PWM modulation scheme with both PWM leading and trailing edges being independently moved to provide the best response to transient loads. The PWM frequency, however, is constant and set by the external resistor between the FS pin and GND.
To further improve the transient response, the ISL6327 also implements Intersil's proprietary Adaptive Phase Alignment (APA) technique. APA, with sufficiently large load step currents, can turn on all phases simultaneously.
With both APP and APA control, ISL6327 can achieve excellent transient performance and reduce the demand on the output capacitors.
Under steady state conditions the operation of the ISL6327 PWM modulator appears to be that of a conventional trailing edge modulator. Conventional analysis and design methods can therefore be used for steady state and small signal operation.
The ISL6327 senses current continuously (no sample-and-hold) on each channel for fast response to changes in inductor current.
Continuous current sensing, APA and APP allow for very high bandwidth response to a load transient events.
Coupled Inductor Details
To further take advantage of the control and sensing features of the ISL6327 the use of coupled inductors in the output filter can be implemented. Coupling 2 phases on a single inductor core allows a reduction in phase inductance for fast transient response without the hit in efficiency due to larger phase ripple currents with an equivalent standard inductor.
With a standard single winding inductor the current waveform is dependant on the voltage at the two terminals of the inductor. The peak-to-peak ripple current in a synchronous buck application is determined by Equation 1.
where VIN is the input voltage, VOUT is the output voltage, L is the standard inductance value, and fS is the switching frequency.
The total output ripple current is determined by the sum of all of the phase currents and its magnitude is reduced by the interleaving of N number of phases.
For a given Vin, Vout and fs, both the channel and total ripple current are determined by L, the standard inductance of each phase.
For the case where there are two inductors coupled on one core, each providing the inductance for one phase in a synchronous buck converter, the ripple current for a single phase is now dependant on the voltages across both inductors as well as the magnetic properties of the coupled inductor.
Consider the two phase coupled inductor drawn in Figure 1.
Note the dot convention. If positive current flows into the dot connected to PHASE1 then current will flow out of the dot connected to PHASE2. This means when one PHASE has a positive current slew rate so will the coupled PHASE. Figure 1 shows example waveforms for a simplified 2 phase case.
IPPsiVIN VOUT– VOUT
L fS VIN
----------------------------------------------------------= (EQ. 1)
ITotalPPsi
VIN N VOUT– VOUTL fS V
IN
----------------------------------------------------------------= (EQ. 2)
FIGURE 1. TWO PHASE COUPLED INDUCTOR RIPPLE CURRENT WAVEFORMS
L1
VOUT
PHASE1
IOUT
PHASE2
Iphase1
Iphase2
PHASE2
PHASE1
IPhase2
IPhase1
IOUT
AN1268 Rev 0.00 Page 3 of 18Oct 26, 2010
ISL6327EVAL5
The equation for peak-to-peak ripple current and total output ripple current are dependent on the magnetic properties of the coupled inductor.
The two winding coupled inductor is essentially a transformer. Like any transformer it will have a specified winding ratio, winding inductance (or self inductance, L), and mutual inductance (LM). Parasitics will include leakage inductance (LLK) and winding resistance (DCR). All these parameters must be considered in optimizing the coupled inductor performance for a given application.
An equivalent circuit for the two phase coupled inductor is shown in Figure 2. For the coupled inductor used in this reference design the windings are symmetrical and the turns ratio is 1:1.
Each winding has a self inductance which is the total inductance that magnetizes the core. In an imperfect transformer some of the flux generated by the current through the winding will not couple through the core to the other winding. The mutual inductance is the portion of the winding inductance that is coupled with the other windings.
The leakage inductance is a measure of how much of the total flux does not couple to the other winding. A system of equations can be used to determine the phase peak-to-peak ripple current equation and total output peak-to-peak ripple current equation.
For the two phase coupled inductor case the phase ripple current is shown in Equation 3:
The total ripple current will be the sum of the phase currents and can be calculated using Equation 4:
Where N is the number of phases in the multiphase converter, and nci is the number of inductors coupled on a single core, in this case nci = 2.
With these equations it can be determined that the output current waveform and therefore the transient response is determined by:
This term is the leakage inductance, LLK, of the two winding coupled inductor. The phase ripple current waveform, or steady state phase ripple current, is determined by the equivalent inductance in Equation 6:
Equations 5 and 6 will be used when selecting components in a two phase coupled inductor application.
Current Sensing
ISL6327 senses phase current continuously for fast response. ISL6327 supports inductor DCR sensing, or resistive sensing techniques. For more detail on the ISL6327 theory of operation please refer to the ISL6327 datasheet.
INDUCTOR DCR SENSING
Choosing the DCR current sense circuitry is straight forward when using standard inductors but a little more complicated when using coupled inductors. Consider the inductor DCR as shown in Figure 3. The channel current IL flowing through the inductor will also pass through the DCR. A simple R-C network across the inductor extracts the DCR voltage.
FIGURE 2. TWO PHASE COUPLED INDUCTOR
DCRLM L - LM
DCR L - LM
N = 1
IPPciVIN VOUT– L LMVOUT–
L2
LM2
– fS
----------------------------------------------------------------------------VOUT
VIN-----------------
= (EQ. 3)
ITotalPPci
VIN N VOUT– VOUTL nci 1– LM– fS V
IN
----------------------------------------------------------------= (EQ. 4)
LTr L nci 1– LM– L LM–= = (EQ. 5)
LSS
VIN VOUT– L2
LM2
–
VIN VOUT– L LMVOUT–----------------------------------------------------------------------------= (EQ. 6)
DCRLM
COUPLED INDUCTOR
VOUT
COUT
IL
LLK
DCR LLK
In
ISEN ILDCR
RISEN------------------=
-
+
ISEN-(n)
CURRENT
SENSE
ISL6327 INTERNAL CIRCUIT
VIN
ISEN+(n)
PWM(n)
ISL6609
RISEN(n)
R
-+ VC(s)
C
CT
FIGURE 3. DCR CURRENT SENSING
AN1268 Rev 0.00 Page 4 of 18Oct 26, 2010
ISL6327EVAL5
If the R-C network components are selected such that the R-C time constant (= R*C) matches the inductor time constant (= L/DCR), the voltage across the capacitor VC is equal to the voltage drop across the DCR, i.e., proportional to the channel current.
With the internal low-offset current amplifier, the capacitor voltage VC is replicated across the sense resistor RISEN. Therefore the current out of ISEN+ pin, ISEN, is proportional to the inductor current.
Equation 7 shows that the ratio of the channel current to the sensed current ISEN is driven by the value of the sense resistor and the DCR of the inductor.
But how is the RC time constant selected in the coupled inductor case? The leakage inductance of the coupled inductor should be used as the inductance in the time constant calculation. The leakage inductance for the two phase coupled inductor is L - Lm.
An equation for selecting the resistor of the RC time constant for a two winding coupled inductor and a given C value is shown in Equation 8. Refer the ISL6327 datasheet for additional component selection guidelines.:
Because of the internal filter at ISEN- pin, one capacitor CT is needed to match the time delay between the ISEN- and ISEN+ signals. Select the proper CT to keep the time constant of RISEN and CT (RISEN x CT) close to 27ns.
Determining The Leakage Inductance of a Coupled Inductor
The leakage inductance of the CI must be determined to design and model with CI's, including using Equations 3-8. There are several methods for accurately determining the leakage inductance per phase of the coupled inductor; two methods are outlined here. Figure 4 depicts an equivalent magnetic circuit for the coupled inductor.
A conventional method for measuring leakage inductance in a transformer is to short the secondary and measure the inductance of the primary. This is a good approximation for a
transformer since the leakage inductance is typically small compared to the self inductance.The coupled inductor in a multiphase application will have a higher percentage of leakage vs. self inductance so additional steps are needed to calculate the actual leakage inductance.
A calibrated bench RLC meter can be used for accurately measuring leakage.
Method 1
1. Leave the secondary winding, pins 2 and 3 in Figure 4, open circuit. The measured inductance from pins 1 to 4 is the primary winding inductance or self inductance. Call this L.
2. Short circuit the secondary winding, pins 2 and 3 in Figure 4. The measured inductance from pins 1 to 4 is the leakage inductance of the primary plus the reflected leakage from the secondary. Call this Ls.
3. For this application the turns ratio is 1:1.
4. The leakage can be calculated using Equation 9:
5. Repeat the above steps to obtain the winding inductance and leakage of the secondary.
Method 2
1. Short pins 4 and 3. The measured inductance will be the sum of the primary and secondary leakages. In the symmetrical, 1:1 winding ratio of the multiphase buck coupled inductor this will be 2*LLK. The average leakage for each winding can be determined by dividing by 2.
IN06006 Specification Using Method 1
The coupled inductor used on the evaluation board is the IN06006. To use this inductor as an example to illustrate method 1 above refer to the IN06006 datasheet for the following steps:
1. The winding inductance listed in the IN06006 datasheet shows 315nH. So, L = 315nH.
2. Shorting the secondary and measuring the primary gives 150nH. Ls = 150nH.
3. The IN06006 winding ratio is 1:1.
4. The leakage inductance of this inductor can be calculated using Equation 9.
So, the leakage inductance for the IN06006 is 87nH. The mutual inductance can be determined by Equation 5. Lm = L - LLK = 228nH.
ISEN ILDCR
RISEN-------------------= (EQ. 7)
RLLK
DCR C----------------------= (EQ. 8)
FIGURE 4. EQUIVALENT MAGNETIC CIRCUIT OF THE COUPLED INDUCTOR
LM
TWO PHASE COUPLED INDUCTOR
LLK2LLK1
1
4
2
3
RLCMETER
LLK L L2
L LS – –= (EQ. 9)
LLK 315 3152
315 150 – – 87nH= =
AN1268 Rev 0.00 Page 5 of 18Oct 26, 2010
ISL6327EVAL5
What Inductor Parameters Do I Use?
The 87nH leakage inductance can be used in Equation 8 to calculate the required RC time constant match for DCR current sensing.
As shown in Equation 5, the leakage inductance determines the total current waveform and therefore the small signal transient response. Use LLK as the phase inductance when calculating the regulator feedback compensation and small signal transient response.
For steady state phase current calculations, use Equation 4. This equation will give the peak-to-peak inductor current waveforms for input ripple calculations, MOSFET selection, and efficiency estimates.
The above analysis shows that a given transient inductance can be used while reducing the phase ripple current vs. an equivalent standard inductor.
Load-Line Regulation and Component Selection
Figure 5 shows that the average current of all active channels, IAVG flows from FB through a load-line regulation resistor, RFB.
The regulated output voltage is reduced by the droop voltage VDROOP. The output voltage as a function of the load current is derived by combining Equation 10 with the sensed current expression defined by the current sense method employed.
Where VREF is the reference voltage, VOFS is the programmed offset voltage, IOUT is the total output current of the converter, RISEN is the sense resistor connected to the ISEN+ pin, RFB is the feedback resistor, N is the number of active channels, and RX is the DCR, or sense resistor, depending on the sensing method.
Therefore, the equivalent load-line impedance (i.e., droop impedance) is:
Overcurrent Protection
ISL6327 has two levels of overcurrent protection. Each phase is protected from a sustained overcurrent condition by limiting its peak current, while the combined phase currents are protected on an instantaneous basis.
In instantaneous protection mode, the ISL6327 utilizes the sensed average current IAVG to detect an overcurrent condition. The average current magnitude can be approximated using Equation 7, the sensed current signal for an individual phase. The average current is continuously compared with a constant 85µA. Once the average current exceeds the reference current, a comparator triggers the converter to shut-down.
For details on how the ISL6327 behaves in reaction to an overcurrent event refer to the ISL6327 datasheet.
For the individual channel overcurrent protection, the ISL6327 continuously compares the sensed current signal of each channel with the 120µA reference current. If one channel current exceeds the reference current, ISL6327 will pull PWM signal of this channel to low for the rest of the switching cycle. This PWM signal can be turned on next cycle if the sensed channel current is less than the 120µA reference current. The peak current limit of individual channel will not trigger the converter to shut-down.
The overcurrent protection level for the above two OCP modes can be adjusted by changing the value of current sensing resistors. In addition, ISL6327 can also adjust the average OCP threshold level by adjusting the value of the resistor from IOUT to GND, R17 on the evaluation board. An overcurrent response will be initiated when the voltage on IOUT reaches 2V. Use Equation 7 to approximate the average current value.
Equation 13 can be used to calculate the value of the resistor RIOUT based on the desired OCP level IAVG, OCP2.
FIGURE 5. OUTPUT VOLTAGE AND LOAD-LINE REGULATION
IAVG
EXTERNAL CIRCUIT ISL6327 INTERNAL CIRCUIT
COMPRC
RFB
FB
VDIFF
VSEN
RGND
-
+VDROOP
ERROR AMPLIFIER
-
+VOUT+
DIFFERENTIALREMOTE-SENSEAMPLIFIER
VCOMP
CC
REF
DAC
RREF
CREF
-
+
VOUT-
IDROOP
VDROOP IAVGRFB= (EQ. 10)
VOUT VREF VOFS–IOUT
N---------------
RXRISEN-------------------RFB
–= (EQ. 11)
RLL
RFBN
-------------RX
RISEN-------------------= (EQ. 12)
RIOUT2V
IAVG OCP2,------------------------------------= (EQ. 13)
AN1268 Rev 0.00 Page 6 of 18Oct 26, 2010
ISL6327EVAL5
Which Phases Should Be Coupled?
Figure 1 has been duplicated in Figure 6 with some changes to the spacing of the PWMs modified to show the effect on the ripple current waveforms.
The bold red and blue waveforms in Figure 6 show an example of how the phase current waveforms will change if the PWM spacing is changed. Best ripple reduction performance is achieved when the two coupled phases are 180 degrees phase-shifted.
The ISL6327 in 6-phase mode fires phases sequentially, PWM1, PWM2, PWM3, PWM4, PWM5, PWM6. So, for optimal phase ripple current reduction PWM1-PWM4, PWM2-PWM5, and PWM3-PWM6 should be coupled.
For optimal layout placement two sequential PWMs should not be placed next to one another. So, from left to right on a PCB, an example placement can be PWM1,PWM4,PWM2, PWM5, PWM3, PWM6.
Modifying the Board For Other ApplicationsAs shipped, the ISL6327EVAL5 is configured for 6 phase operation, a VR11 VID of 1.35V, and designed for operation up to 130A with a loadline of 1.25m. The coupled inductors on board are IN06006.
The inductor footprints on the board are large enough to accommodate the footprints of other coupled inductors for evaluation purposes.
The following procedure can be used to modify the board for 4 phase evaluation.
Four Phase VR11 05A Configuration, LL = 1m1. Change Feedback Compensation: R4 = 2.32k, R7 = 100, C6 = 390pF, C5 = 330pF, R5 = 9.09k, C7 = 33pF
2. Change the IOUT resistor to decrease the overcurrent set point: R17 = 36.5k which will give IOC = 120A
3. Change the DCR sense resistors: R22, R24, R26, R28, R30, R32 = 1.3k
4. Move jumper hats on PWM5 and PWM6 pouts: Move hats on JP_4P_SEL1 and JP_5P_SEL2 from pins 2 and 3 to short pins 1 and 2. This will disable PWM5 and PWM6
5. The 6 phase board is configured with (40) 10µF ceramic capacitors in the output filter. For 4 phases 05A configuration add 10 to 20 additional 10µF ceramic capacitors to the output filter. There are plenty of additional 1206 footprints around the socket to do this.
6. Remove unused power stage: Remove INDUCTORS L3, MOSFETS Q3L1, Q3U1, Q6L1, Q6U1, DRIVERSU4, and U7.
7. Remove R79 which is connecting PWM5 to DRIVER U6
8. Place a 0 resistor on R80 to connect PWM3 to DRIVER U6.
9. On the back of the PCB remove R84 and R85. Place 0 resistors on R90 and R91.
10. Follow the Quick Start Evaluation procedure on page 1 to power up the board.
FIGURE 6. COUPLED INDUCTOR CURRENT WAVEFORMS
L1
VOUT
PHASE1
IOUT
PHASE2
Iphase1
Iphase2
PHASE2
PHASE1
IPhase2
IPhase1
IOUT
AN1268 Rev 0.00 Page 7 of 18Oct 26, 2010
ISL6327EVAL5
ISL6327EVAL5 Six Phase Performance
FIGURE 7. START-UP SEQUENCE FIGURE 8. SHUT-DOWN SEQUENCE
FIGURE 9. NO LOAD RIPPLE ~10mV FIGURE 10. 130A RIPPLE ~12mV
FIGURE 11. TRANSIENT RESPONSE 20A to 120A IN 1200A/µs FIGURE 12. TRANSIENT RESPONSE 120A to 20A IN 1200A/µs
EN5V/DIV
VCORE0.5V/DIV
VR_RDY5V/DIV
0.5ms/DIV
VCORE0.5V/DIV
EN5V/DIV
VR_RDY5V/DIV
VCORE0.5V/DIV
50µs/DIV
5µs/DIV
VCORE20mV/DIV
5µs/DIV
VCORE20mV/DIV
10µs/DIV
VCORE50mV/DIV
ILOAD1V/DIV
10µs/DIV
VCORE50mV/DIV
ILOAD1V/DIV
AN1268 Rev 0.00 Page 8 of 18Oct 26, 2010
ISL6327EVAL5
FIGURE 13. VR EFFICIENCY VIN = 12V, VID = 1.35V, LL = 1.25m, VOUT MEASURED AT INDUCTOR
FIGURE 14. VCORE LOADLINE REGULATION FROM 0A TO 150A
FIGURE 15. VID-ON-THE-FLY OPERATION 0.6V to 1.55V
ISL6327EVAL5 Six Phase Performance (Continued)
72
74
76
78
80
82
84
86
88
90
92
0 10 30 50 70 90 110 130 150
EF
FIC
IEN
CY
(%
)
IOUT (A)
1.10
1.15
1.20
1.25
1.30
1.35
0 20 40 60 80 100 120 140 160
VO
UT (
V)
IOUT (A)
VMIN
VMAX
VOUT
.5ms/DIV
VCORE0.5V/DIV
AN1268 Rev 0.00 Page 9 of 18Oct 26, 2010
ISL6327EVAL5
ISL6327EVAL5 Four Phase Performance
FIGURE 16. START-UP SEQUENCE FIGURE 17. SHUT-DOWN SEQUENCE
FIGURE 18. NO LOAD RIPPLE ~6mV FIGURE 19. 130A RIPPLE ~11mV
FIGURE 20. TRANSIENT RESPONSE 35A to 100A IN 50ns FIGURE 21. TRANSIENT RESPONSE 100A to 35A IN 50ns
EN5V/DIV
VCORE0.5V/DIV
VR_RDY5V/DIV
0.5ms/DIV
VCORE0.5V/DIV
EN5V/DIV
VR_RDY5V/DIV
VCORE0.5V/DIV
50µs/DIV
5µs/DIV
VCORE20mV/DIV
5µs/DIV
VCORE20mV/DIV
10µs/DIV
VCORE50mV/DIV
ILOAD1V/DIV
10µs/DIV
VCORE50mV/DIV
ILOAD1V/DIV
AN1268 Rev 0.00 Page 10 of 18Oct 26, 2010
ISL6327EVAL5
SummaryThe ISL6327EVAL5 evaluation board provides a high performance VRD solution highlighting the ISL6327 advanced multiphase controller with the use of a coupled inductor and low capacitance output filter.
For detailed theory of operation, component selection and layout guidelines refer to the ISL6327 datasheet.
The following pages provide a board schematic and bill of materials to support implementation of this and similar solutions.
ReferencesIntersil documents are available on the web at www.intersil.com.
[1] ISL6327 Data Sheet, Intersil Corporation, File No. FN9276
[2] ISL6609 Data Sheet, Intersil Corporation, File No. FN9221
[3] IN06006 Coupled Inductor Datasheet ICE Components, www.icecomponents.com
FIGURE 22. VR EFFICIENCY VIN = 12V, VID = 1.4V, LL = 1.0m, VOUT MEASURED AT INDUCTOR
FIGURE 23. VCORE LOADLINE REGULATION FROM 0A TO 100A
ISL6327EVAL5 Four Phase Performance (Continued)
72
74
76
78
80
82
84
86
88
90
92
0 10 20 30 40 50 60 70 80 90 100 110
EF
FIC
IEN
CY
(%
)
IOUT (A)
1.25
1.30
1.35
1.40
0 20 40 60 80 100 120
VO
UT (
V)
IOUT (A)
VMIN
VMAX
VOUT
AN1268 Rev 0.00 Page 11 of 18Oct 26, 2010
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ISL6
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AL5
Vc5
ISEN5-
ISEN6-
ISEN1+
ISEN2-
ISEN3-
ISEN4-
ISEN1-
PWM1
PWM2
PWM5
PWM3
PWM6
PWM4
ISEN2+
ISEN3+
ISEN4+
ISEN5+
ISEN6+
For 6phase operationplace all 4 PWM jumperson pins 2 and 3
CF268pCF268p
C180.1uC180.1u
R25 402R25 402
R27 402R27 402
R29 402R29 402
C130.1uC130.1u
C190.1uC190.1u
C160.1uC160.1u
R31 402R31 402
CF368pCF368p
R241.21kR241.21k
CF468pCF468p
C210.1uC210.1u
CF568pCF568p
R21 402R21 402
CF168pCF168p
CF668pCF668p
C140.1uC140.1u
R301.21kR301.21k
C120.1uC120.1u
C220.1uC220.1u
C200.1uC200.1u
C150.1uC150.1u
R321.21kR321.21k
R221.21kR221.21k
R23 402R23 402
R281.21kR281.21k
R261.21kR261.21k
C170.1uC170.1u
C110.1uC110.1u
Controller Circuit
VCC5
VCC5
VCC12
VCC5
Vc5
VCC5
Vc5
Vc5
VCC12
VCC5 VCC5
RGND
VSENVTTVRSEL
VID0VID1VID2VID3VID4VID5VID6VID7
ntroller circuit
Thermistor
IOC target 169A
R55
10k
R55
10k
C10DNSC10DNS
R91kR91k
RN26.8kRN26.8k
C2DNSC2DNS
TP12GND1TP12GND1
R151kR151k
REDGREEN
CR2VR_RDY
REDGREEN
CR2VR_RDY
12
34
EN1EN1
1 3
26 4
JP_5P_SEL2
jumper_3pin
JP_5P_SEL2
jumper_3pin
12
3
C81uC81u
R512.1kR512.1k
R1141.2kR1141.2k
TP18OFSTP18OFS
JP_3P_SEL3
jumper_3pin
JP_3P_SEL3
jumper_3pin
12
3
TP9GND1TP9GND1
R44.32kR44.32k
R341.5kR34
1.5k
R181KR181K
C910nC910n
R53DNS
R53DNS
TP11GND1TP11GND1
TP3IOUTTP3IOUT
TP14VR_RDYTP14VR_RDY
R12100kR12100k
TP17COMPTP17COMP
U1ISL6327U1ISL6327
VID71
IDROOP16
VDIFF17
VSEN19 RGND18
EN_VTT 41
VR_RDY45
VID62VID53VID44VID35VID26VID17VID08VRSEL9
VR_FAN 46
VR_HOT 47
TM 48
OFS10
FS42
EN_PWR 40
ISEN5+ 23ISEN5- 22PWM5 24
ISEN3+ 35ISEN3- 34PWM3 36
ISEN1+ 32ISEN1- 33PWM1 31
ISEN2+ 26ISEN2- 27PWM2 25
ISEN4+ 29ISEN4- 28PWM4 30
ISEN6+ 38ISEN6- 39PWM6 37
SS43
VCC21
DAC12
REF13
COMP14
FB15
OVP 44
IOUT 11
GND49
TCOMP20
Q242N7002
Q242N7002
1
23
C733pC733p
R5410KR5410K
R210R210
TP15VR_FANTP15VR_FAN
R56DNSR56DNS
JP_4P_SEL1
jumper_3pin
JP_4P_SEL1
jumper_3pin
12
3
C4DNSC4DNS
R1020kR1020k
R7100R7100
C6390pFC6390pF
TP5DACTP5DAC
C1DNS
C1DNS
C5330pFC5330pF
R1310kR1310k
C48100pC48100p
TP8GND1TP8GND1
R161KR161K
R36 0R36 0
R310R310
TP4REFTP4REF
R82.2R82.2
TP16VR_HOTTP16VR_HOT
JP_2P_SEL1
jumper_3pin
JP_2P_SEL1
jumper_3pin
12
3
R35
0
R35
0
TP6VDIFFTP6VDIFF
R1741.2kR1741.2k
R331kR331k
R141kR141k
TP7TMTP7TM
R110R110
RC1100KRC1100K
TP13ENTP13EN
TP10GND1TP10GND1
C3DNSC3DNS
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327
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TitleSize Rev
D t Sh t f
AISL6327 CI EVALUATION 5 BOARDB
2 5F id J l 28 2006
Intersil RTP
Intersil Corporation
TitleSize Rev
D t Sh t f
AISL6327 CI EVALUATION 5 BOARDB
2 5F id J l 28 2006
Intersil RTP
Intersil Corporation
TitleSize Rev
D t Sh t f
AISL6327 CI EVALUATION 5 BOARDB
2 5F id J l 28 2006
Intersil RTP
Intersil Corporation
to test point
Optional SP caps
CT32.2nCT32.2n
CO7310u
CO7310u
CO7410u
CO7410u
CO7610u
CO7610u
CO8010u
CO8010u
CO83330uCO83330u
CO7910u
CO7910u
7210u72
10u
CO81330uCO81330u
CO7810u
CO7810u
CO82330uCO82330u
CO7510u
CO7510u
CO7710u
CO7710u
VOUT2Vout-VOUT2Vout-
Output Capacitors and LGA775 VID Connections
VCC_DIE
VSS_DIE
RGND
VSEN
VCORE
VTTVRSEL
VCORE
VTTVID1
VTTVID2
VTTVID3
VTTVID4
VTTVID5
VTTVID6
VTTVID7
VTTVID0
VSEN
RGND
Place those resistors and caps close
Install R39, R41 for SocketSensing connection
Install R40, R42 for Die Sensing connection
Place those 10 caps on top side
Place those 9 caps inside of CPU carvity on top side
Those caps are for Low frequency operation only. Do not install for high frequncy operation.
Place those 15 caps on bottom side Place those 9 caps inside CPU Carvity area on bottom side
Place those 25 caps on top side
For 6phase operation and 100A load step;board is populated with 40*10uF 1206capacitors
CO3810u
CO3810u
CO7110u
CO7110u
CO4210u
CO4210u
CO5910u
CO5910u
CO2510u
CO2510u
CO9560uCO9560u
CO2910u
CO2910u
CO4610u
CO4610u
CT11u
CT11u
CO6310u
CO6310u
CO5560uCO5560u
CO6710u
CO6710u
R39
0
R39
0
CO3310u
CO3310u
CO5010u
CO5010u
CO12560u
CO12560u
R_SEL2 DNSR_SEL2 DNS
CO3710u
CO3710u
TP1VCORE
TP1VCORE
CT22.2nCT22.2n
CO13100u
CO13100u
CO5710u
CO5710u
CO2410u
CO2410u
CO4560uCO4560u
CO4110u
CO4110u
R43DNSR43DNS
CO15100u
CO15100u
CO4510u
CO4510u
VTT_R1
0
VTT_R1
0
CO6210u
CO6210u
CO1560uCO1560u
CO2810u
CO2810u
CO6610u
CO6610u
CO3210u
CO3210u
CO4910u
CO4910u
R42 0R42 0
CO6810u
CO6810u
CO5310u
CO5310u
BNC1DNSBNC1DNS
1
4 5
23
R40 0R40 0
CO7010u
CO7010u
CO3610u
CO3610u
CO16100u
CO16100u
CO2310u
CO2310u
GND1 GNDGND1 GND1
CO4010u
CO4010u
COCO
R410R410
CO5610u
CO5610u
CO20100u
CO20100u
CO6110u
CO6110u
CO2710u
CO2710u
VTT_R2
0
VTT_R2
0
CO2560uCO2560u
\CO4410u
\CO4410u
CO17100u
CO17100u
CO4810u
CO4810u
CO6510u
CO6510u
CO3110u
CO3110u
VCORE1 V_COREVCORE1 V_CORE1
CO21100u
CO21100u
U100
VCC
VSS
AM2
AL5
AM3
AL6
AK4
AL4
AM5
AM7
AN5
AN6
AN3
AN4
AN7
CO8560uCO8560u
CO3510u
CO3510u
CO5210u
CO5210u
CO14100u
CO14100u
CO22100u
CO22100u
CO5410u
CO5410u
CO7560uCO7560u
CO3910u
CO3910u
CO18100u
CO18100u
CO11560u
CO11560u
CO2610u
CO2610u
CO4310u
CO4310u
CO5510u
CO5510u
CO6010u
CO6010u
VOUT1Vout+VOUT1Vout+
CO6410u
CO6410u
CO10560uCO10560u
C66DNSC66DNS
CO5810u
CO5810u
CO3010u
CO3010u
CO4710u
CO4710u
CO3560uCO3560u
CO3410u
CO3410u
CO19100u
CO19100u
CO6910u
CO6910u
CO5110u
CO5110u
CO6560uCO6560u
R74DNSR74DNS
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TitleSizeISL6327 CI EVALUATIONC
Intersil RTP
Intersil Co
TitleSizeISL6327 CI EVALUATIONC
Intersil RTP
Intersil Co
TitleSizeISL6327 CI EVALUATIONC
Intersil RTP
Intersil Co
or
used
used
Power Stage
D
C
B
A
VINF
VINF
VCC5
VCC12
VINF
VINF
VINF
VINF
ISEN2-
ISEN3-
PWM1
ISEN1-
ISEN1+
ISEN2+
ISEN3+
ISEN5-
ISEN6-
PWM6
PWM5
ISEN4-
ISEN4+
ISEN6+
ISEN5+PWM3
PWM2
PWM2
PWM4
PWM3
ISEN3-
ISEN3+
ISEN2-
ISEN2+
(OSCON)
Power StagePut those 2 test points close to input inductor
L1 is used for 6-phase 4-phase mode
L2 is only for 6-phase
L3 is only for 6-phase
U3isl6609U3isl6609
BT1
PWM2
GN
D3
LG4
VCC 5
EN 6
PH7
UG
8G
L9
RS3
3.3
RS3
3.3Q3L1HAT2165HQ3L1HAT2165H
TPVCORE1VCORETPVCORE1VCORE
U4isl6609U4isl6609
BT1
PWM2
GN
D3
LG4
VCC 5
EN 6
PH7
UG
8G
L9
U7isl6609U7isl6609
BT1
PWM2
GN
D3
LG4
VCC 5
EN 6
PH7
UG
8G
L9
C6010uC6010u
RS5
3.3
RS5
3.3
C540.22uC540.22u
C6210uC6210u
R90DNSR90DNS
R770R770
U5isl6609U5isl6609
BT1
PWM2
GN
D3
LG4
VCC 5
EN 6
PH7
UG
8G
L9
C2610u
C2610u
C5810uC5810u
Q5L1HAT2165HQ5L1HAT2165H
C280.22uC280.22u
CS22200pCS22200p
RV10RV10
CS12200pCS12200p
C3410u
C3410u
C5710uC5710u
C231uC231u
C311uC311u
Q1L1HAT2165HQ1L1HAT2165H
C2510u
C2510u
R880R880
C6110uC6110u
RS2
3.3
RS2
3.3
C631uC631u
Q5U1HAT2168HQ5U1HAT2168H
VIN2Vin-VIN2Vin-
L2
IN06006
L2
IN06006
1
2
3
4
R92DNSR92DNS
Q3U1HAT2168HQ3U1HAT2168H
CS42200pCS42200p
RS6
3.3
RS6
3.3
C240.22uC240.22u
TPGND1GNDTPGND1GND
CS52200pCS52200p R85
0R850
C5910uC5910u
R780R780
C320.22uC320.22u
C271uC271u
C560.22uC560.22u
R590 R590
C2910u
C2910u
C3310u
C3310u
C3010u
C3010u
Q1U1HAT2168HQ1U1HAT2168H
R93DNSR93DNS
Q4L1HAT2165HQ4L1HAT2165H
CI_1470u
CI_1470u
RS1
3.3
RS1
3.3
U2isl6609U2isl6609
BT1
PWM2
GN
D3
LG4
VCC 5
EN 6
PH7
UG
8G
L9
R610R610
Q2L1HAT2165HQ2L1HAT2165H
Q6L1HAT2165HQ6L1HAT2165H
VIN1Vin+VIN1Vin+
R81DNSR81DNS
R580 R580
R80DNSR80DNS R84
0R840
L_IN1150nL_IN1150n
R600R600
R790R790
R620R620
L1
IN06006
L1
IN06006
1
2
3
4
R860R860
RS4
3.3
RS4
3.3
U6isl6609U6isl6609
BT1
PWM2
GN
D3
LG4
VCC 5
EN 6
PH7
UG
8G
L9
C641uC641u
Q4U1HAT2168HQ4U1HAT2168H
R820R820
R91DNSR91DNS
L3
IN06006
L3
IN06006
1
2
3
4CS32200pCS32200p
Q6U1HAT2168HQ6U1HAT2168H
R870R870
C550.22uC550.22u
R630R630
C651uC651u
Q2U1HAT2168HQ2U1HAT2168H
CS62200pCS62200p
R890R890
AN
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5V
VTTVID0
VTTVID1
VTTVID2
VTTVID3
VTTVRSEL
VTTVID4
VTTVID5
VTTVID6
VTTVID7
VID3
VID4
VID5
VID6
VID7
VID0
VID1
VID2
TitleSizeISL6327 CI EVALUATION 5 BOARB
Intersil RTP
Intersil Corporation
TitleSizeISL6327 CI EVALUATION 5 BOARB
Intersil RTP
Intersil Corporation
TitleSizeISL6327 CI EVALUATION 5 BOARB
Intersil RTP
Intersil Corporation
J_VID5jumper_3pinJ_VID5jumper_3pin
12
3
RVID1
2k
RVID1
2k
J_VID4jumper_3pinJ_VID4jumper_3pin
12
3
RVID4
2k
RVID4
2k
RVID7
2k
RVID7
2k
J_VID3jumper_3pinJ_VID3jumper_3pin
12
3
J_VID0jumper_3pinJ_VID0jumper_3pin
12
3
RVID2
2k
RVID2
2k
RVID5
2k
RVID5
2k
J_VID2jumper_3pinJ_VID2jumper_3pin
12
3
R_SEL1
0
R_SEL1
0
J_VID1jumper_3pinJ_VID1jumper_3pin
12
3
RVID02kRVID02k
J_VID7jumper_3pinJ_VID7jumper_3pin
12
3
RVID3
2k
RVID3
2k
RVID6
2k
RVID6
2kJ_VID6jumper_3pinJ_VID6jumper_3pin
12
3
VID Generator and Input Power Connectors
5V_6P
+5V
+5V
+5V
+5V
+5V
VCC12
VCC55V
or and Input power connectors
VID Code
VR11/VR10IPF/IA32
Repetitious/ManualDEMO/VTT
5V_GND15V_GND1
R450R450
C500.01uC500.01u
R4910kR4910k
R5010kR5010k
R5110kR5110k
C5233pC5233p
SW2SW DIP-8SW2SW DIP-8
C4710uC4710u
R5210kR5210k
Y1Y1
C4910uC4910u
R4710kR4710k1
2 3 4 5 6 7 8 9
10
U8PIC16F874A-PTU8PIC16F874A-PT
RC032RC135RC236RC3/SCL37RC4/SDA42RC543RC6/TX44RC7/RX1
RD038RD139RD240RD341RD42RD53RD64RD75
RE025RE126RE227
RB0 8RB1 9RB2 10RB3 11RB4 14RB5 15RB6 16RB7 17
RA0 19RA1 20RA2 21RA3 22RA4 23RA5 24
OSC1 30
OSC2 31
GND16 GND29
VCC7VCC128
NC3 34NC2 33
NC 12NC1 13
MCLR 18
12V_GND112V_GND1
SW3VID LoadSW3VID Load
1 32 4
STEP1StepSTEP1Step
SW1SW DIP-4SW1SW DIP-4
C5333pC5333p
C511uC511u
12V112V1 R830R830
12V_PWR1
ATX 12V AUX POWER
12V_PWR1
ATX 12V AUX POWER
GND1
GND02 12V 4
+12V 3
55
5V15V1
TP2TPTP2TP
5V_PWR124 PIN POWER5V_PWR124 PIN POWER
+3.3V1+3.3VA2
+12V1B11
+5V4+5VA6 GND5 19
NC 20
+5VSB9
-12V14
GND 3GND0 5GND1 7
+3.3VC13 GND2 15
PS_ON#16
GND3 17
+3.3VB12
GND4 18
PWR_OK 8
+12V1A10
2525
+5VB21+5VC22+5VD23
GND6 24
R440R440
R4610kR4610k
R4810kR4810k
ISL6327EVAL5
Bill of MaterialsQTY REF DESIGNATOR DESCRIPTION VENDOR VENDOR P/N PKG
3 C52, C53, C7 33pF, 50V COG 0603 Cap Various REEL
1 C48 100pF, 50V COG 0603 Cap Various REEL
6 CF1, CF2, CF3, CF4, CF5, CF6 68pF, 50V X7R 0805 Cap Various REEL
1 C5 330pF, 50V X7R 0603 Cap Various BAG
1 C6 390pF 50V COG 0603 Cap Various BAG
4 C3, C2, CT2, CT3 2.2nF, 50V X7R 0603 Cap NIC NMC0603X7R222K REEL
2 C9, C50 10nF, 50V X7R 0603 Cap NIC NMC0603X7R103K REEL
12 C12, C14, C16, C18, C20, C22, C11, C13, C15, C17, C19, C21
0.1µF, 16V X7R 0603 Capacitor MURATA BAG
6 C24, C28, C32, C54, C55, C56 0.22µF, 50V Y5V 0603 Cap MURATA GRM188F51H224Z BAG
8 C8, C23, C27, C31, C51, C63, C64, C65 1µF, 16V X5R 0603 Cap MURATA GRM188R61C105K BAG
1 CT1 1µF, 16V X7R 1206 Cap MURATA GRM319R71C105K BAG
1 C49 10µF, 16V Y5V 0805 Cap MURATA GRM21BF51C106Z BAG
58 CO23, CO24, CO25, CO26, CO27, CO28, CO29, CO30, CO31, CO32, CO33, CO34, CO35, CO36, CO37, CO38, CO39, CO40, CO41, CO42, CO43, CO44, CO45, CO46, CO47, CO48, CO49, CO50, CO51, CO52, CO53, CO54, CO55, CO56, CO57, CO58, CO59, CO60, CO61, CO62, CO63, CO64, CO65, CO66, CO67, CO68, CO69, CO70, CO71, CO72, CO73, CO74, CO75, CO76, CO77,
CO78, CO79, CO80
10µF, 6.3V X7R 1206 Capacitor MURATA GRM31CR70J106M REEL
0 100µF, 6.3V X5R 1210 Capacitor MURATA GRM31CR60J107M REEL
13 C25, C26, C29, C30, C33, C34, C57, C58, C59, C60, C61, C62
10µF, 16V X5R 1206 Capacitor MURATA GRM31CR61C106K BAG
1 CI_1 470µF, 16V Sanyo OSCON Sanyo 16SEPC470M BAG
29 R39, R41, R58, R59, R60, R61, R62, R35, R36, R63, R75, R76, R79, R82,
VTT_R1, VTT_R2, R_SEL1, R82, R79, R88, R89, R77, R78, R84, R85, R86,
R87, R40, R42
0 5% Resistor; 0603 Various REEL
4 R44, R45, R83, RV1 0 5% Resistor; 1206 Various REEL
1 R8 2.2 5% Resistor; 1206 Various REEL
6 RS1, RS2, RS3, RS4, RS5, RS6 3.3 Resistor, 5%, 1206 Various REEL
3 R1, R2, R3 10 5% Resistor; 0603 Various REEL
6 RF1, RF2, RF3, RF4, RF5, RF6 12 1% Resistor; 0603 Various REEL
6 R21, R23, R25, R27, R29, R31 402 1% Resistor; 0603 Various REEL
1 R7 200 1% Resistor; 0603 Various REEL
6 R9, R15, R16, R18, R33, R34 1k 1% Resistor; 0603 NIC NRC06F1001TR REEL
8 RVID0, RVID1, RVID2, RVID3, RVID4, RVID5, RVID6, RVID7
2k 1% Resistor; 0603 Various BAG
1 R4 4.32k 1% Resistor; 0603 Various BAG
6 R22, R24, R26, R28, R30, R32 1.21k 1% Resistor; 0603 Various BAG
10 R13, R43, R46, R48, R49, R50, R51, R52, R54, R55
10k 1% Resistor; 0603 NIC NRC06F1002TR REEL
1 R5 12.1k 1% Resistor; 0603 NIC NRC06F1002TR REEL
1 R10 20k 1% Resistor; 0603 NIC NRC06F2002TR REEL
AN1268 Rev 0.00 Page 16 of 18Oct 26, 2010
ISL6327EVAL5
2 R11, R17 41.2k 1% Resistor; 0603 NIC NRC06F1003TR REEL
2 R12, RC1 100k 1% Resistor; 0603 NIC NRC06F1003TR REEL
1 R47 10k x 8 Resistor Array AVX RNA4A8E103JT REEL
1 RN2 THERM_6.8K_0805 Vishay NTHS0805N02N6801 BAG
3 L1, L2, L3 87nH/64A Coupled Inductor (0.55m DCR) ICE IN-06006 DNS
1 LIN_1 150nH/40A Inductor (0.48m DCR) Cooper FP4-150 REEL
6 Q1U1, Q2U1, Q3U1, Q4U1, Q5U1, Q6U1
Upper MOSFETs Hitachi HAT2168H or RJK0305
BAG
6 Q1L1, Q2L1, Q3L1, Q4L1, Q5L1, Q6L1 Lower MOSFETs Hitachi HAT2165H or RJK0301
BAG
1 Y1 Crystal 16.000 MHz HC49/US ECS ECS-160-20-4 BAG
6 U2, U3, U4, U5, U6, U7 Sync Rec Buck Drvr 5V QFN Intersil ISL6609CR (QFN) TUBE
1 U1 Multiphase Buck Voltage Regulator Intersil ISL6327CR BAG
1 U8 8-BIT Microchip Cntrl Microchip PIC16F874A-I/PT BAG
2 CR1, CR2 4P LED 3X2.5MM SMD Luminex SSL-LXA3025IGC BAG
1 Q24 N-Ch MOSFET SOT-23 Fairchild 2N7002 BAG
1 SW1 4 Pin DIP Switch CTS 219-4LPST TUBE
1 SW2 8 Pin DIP Switch CTS 219-8LPST TUBE
1 SW3 Momentary Pushbutton Switch Panasonic EVQ-QWT03W BAG
1 EN1 Toggle Switch Mini SPDT SMD ITT GT11MSCKETR BAG
1 5V_PWR1 24 Pin ATX Connector Molex 39-29-9242 BAG
1 12V_PWR1 4 Pin Power Connector Molex 39-29-9042 BAG
17 STEP1, VIN1, VIN2, VOUT1, VOUT2, VCORE1, TP1, TP2, TP3, TP4, TP5,
TP13, TP14, TP15, TP16, TP17, TP18
Test Points Keystone 5002 BAG
5 TP8, TP9, TP10, TP11, TP12 Test Points, Turret 0.281 Height Keystone 1514-2 BAG
1 TP1 O'scope Probe Test Point Tektronix K131-4244-00 BAG
12 J_VID0, J_VID1, J_VID2, J_VID3, J_VID4, J_VID5, J_VID6, J_VID7,
JP_4P_SEL1, JP_2P_SEL1, JP_3P_SEL3, JP_5P_SEL2
3 Pin Header AMP/TYCO A26512-ND BAG
2 5V1, 12V1 Banana Jack Keystone 7006K BAG
2 5V_GND1, 12V_GND1 Banana Jack Keystone 7007K
1 BNC1 BNC connector 31-5329-52RFX BAG
2 VCORE1, GND1 Terminal Lugs Burndy KPA8CTP BAG
5 5 on the back of the board Bumpons
1 U100 CPU socket FOXCONN LGA775 TRAY
47 R53, R56, C1, C6, C7, C10, R_SEL2, CO1, CO2, CO3, CO4, CO5, CO6, CO7, CO8, CO9, CO10, CO11, CO12, CO81, CO82, CO83, R81, R80, R92, R93, R90,
R91, R43, R74, C66, CS1-6, CO13, CO14, CO15, CO16, CO17, CO18,
CO19, CO20, CO21, CO22
Not Populated List DNS
Bill of Materials (Continued)
QTY REF DESIGNATOR DESCRIPTION VENDOR VENDOR P/N PKG
AN1268 Rev 0.00 Page 17 of 18Oct 26, 2010
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