steer sim1
TRANSCRIPT
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NC STATE UNIVERSITY
Simulation and Modeling ofLarge Microwave and
Millimeter-Wave Systems,
Part 1Michael Steer
with
Nikhil Kriplani, Carlos Christofferson
and Shivam Priyadarshi
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Copyright 2009 to 2011 by M. Steer, N. Kriplani and S. Priyadarshi
Not to be posted on the web or distributed electronically without permission.
http://www.freeda.org
http://www.freeda.org/http://www.freeda.org/ -
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fREEDA
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Open Source / Open
LicensingBSD License (Open to
companies to do what they
want), well almost there.
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Essential Concepts for
Multi-Physics Modeling
Integration of multi physics problem into the circuitmodeling domain
Object Oriented Approach
Global Modeling EM Interconnect Modeling Digital Macromodeling Opto Electronic Modeling Quantum Modeling Molecular Modeling
Materials Modeling Bio / Chemical Modeling
Interfaces
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Universal Error Concept (Energy Norm)
Universal error concept:AT A TERMINAL
FLUX = 0
All Potent ials are the SAME
MECHANICAL
THERMAL
ELECTRICAL
FORCE
HEAT
CURRENT
I
Flow
POSITION
TEMPERATURE
V
Effort
INERTIAL REFERENCE FRAME
ABSOLUTE ZERO
LOCAL GROUND
LOCAL REFERENCE NODE
For each state variable xthere must be a flow and an effort
contribution.
i(t) v(t)
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Many Unique Models
EM Interface (TD and FD) Electro-Thermal
Dynamic Range
Time Delay
Large Signal Noise
Electro-Optic
Molecular Diode
n+ poly
STI STI
tox
Vg
oxide
L
p type
Jg (tunneling)
V_ref
MOSCAPWorlds first implementation
E.G. The tunnel process cannot be expressed as a
current-charge-voltage expression as Spice
requires. Instead use state variables to implement
tunneling correctly. 6
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Circuit Theory
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Background Reading
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Background Reading
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Microstrip Model In a Field Simulator Voltages Are Determined By
Integrating The Electric Field Along a Path
In Microstrip Problems the Field is Integrated OverThe Paths Shown to Obtain V
The Path of Integration Matters
The Dashed Path Yields a Different Value of V2
V1
V2
Not the same
point electrically.
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Microstrip Model
Network Model:11 12
21 22
S S
S S
V1 V2
REFREF
REF REF
V2V1
But a (SPICE) Circuit
does not have two
reference terminals.
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Global Reference Node
Perfect Ground Plane Assumed (No Retardation Effects)
In A Field Simulator Voltages Are Determined ByIntegrating The Electric Field Along a Path
In Microstrip Problems the Field is IntegratedOver The Paths Shown to Obtain
The Path of Integration Matters The Dashed Path Yields a Totally Different
Value
of
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Conventional Microwave Circuits(e.g. Microstrip)
V1
V2
V and1 V2
V2
Current Microwave
Simulators (Linear, Harmonic
Balance, Transient) are
Based on Nodal VoltageDescriptions
To Use Nodal Voltages There
Must Be a Common
Reference Node
Field Simulators Currently
Require A Common
Reference Ground
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Local reference node concept This avoids non-physical connections and therefore is
fundamental for the analysis of spatially distributed
circuits as well as for simultaneous thermal-electricalsimulations.
V1 V2REFREF
LOCAL REFERENCE
TERMINAL
How to extend this beyond two terminal ports?
Our common view of
a port is that it has
two terminals
i1
i1
i2
i2
1 2
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Non- fREEDA fREEDA
Circuit
Circuit
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Circuit vs. Network Graph
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Circuit Graph
Network Graph
Concept of Spice
CIRCUIT GRAPH
NETWORK GRAPH
Concept of fREEDA
Must use two circuit graphs to
represent a general circuit
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Network Graph
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A
N
U
TS
R
Q
P
O
F
L
G
H
IB
C
J
D
KE
A node
a edgea
b
Information is stored in fREEDA as a Network Graph but the
difference between a terminal and an element is retained.
c
d
e
f
A
B
C
D
E
F
G
H
I
J
L
M
K
N
O
P
Q
R
S
T
U
ab
c
d
ef
hg
g
h
NETWORK GRAPH
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Modeling Concept
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SPATIALLY
DISTRIBUTED
CIRCUIT
LINEAR
CIRCUITNONLINEAR
NETWORK
THERMAL
NETWORK
LINEAR NETWORK
Nonlinear Analysis Must be Point of Integration
UseSPICE-like & HARMONIC BALANCE analyses
Use Existing Domain Specific Analyses
E.G. Thermal, Field
Behavioral Modeling Is the Key to Using Results of
One Simulator In Another
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Modeling Scope
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Can handle
11
2 32 31 12 2 3 3
1 1 1
( )( )( ), , ( ), , , ,
( ) ( )( ) ( )( ) , , , , , ,
( ), , ( )
nn
n n
n
dx tdx tx t x t
dt dt
d x t d x t d x t d x t y t F
dt dt dt dt x t x t
=
Where y(t) is either an i(t) or a v(t).
Also in any type of analysis we want dy/dx The exact derivatives (w.r.t. t imeor frequency etc.) we want depend on the type of analysis we are doing
(transient, wavelet, harmonic balance). The derivatives needed are calculated
using ADOL-C under control of the analysis rout ines. This is why the same
model can be used in any type of analysis.
ADOL-C is one of the many support libraries.
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fREEDAUnique Feature:
Nonlinear devices models based onstate variables:
This provides great flexibility forthe design of new models. All ofthe analyses are state-variable-based, including a time marchinganalysis (different integration
methods available) and a uniquewavelet transient analysis.
The state variables can be chosento achieve robust numericalcharacteristics.
The calculation of derivatives arefree of truncation errors at a small
multiple of the run time requiredto evaluate the original functionwith little additional memoryrequired. (ADOLC)
CONVENTIONAL DIODE MODEL
STRONG NONLINEARITY
v
i
v
x
x
NEW
NEW
MODERATE NONLINEARITY
+
ix
v
=
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Bottom
DBR
TopDBRp-contact
Oxide
Light
Output
Active
Regionn-contact
VCSEL Modeling
Single Mode Rate Equations
Carrier density
dN(t)/dt =i(I(t)-IL(T))/ N(t)/nr G(T)(N(t)-N0(T))S(t)/(1+S(t))
Photon densitydS(t)/dt = -S(t)/p+ N(t)/r+ G(T)(N(t)-N0(T))S(t)/(1+S(t))
Temperature
dT(t)/dt = -T(t)/th+ (T0+(I(t)V(t)-P0(t))Rth)/th
Leakage Current
IL = IL0exp[(-a0+ a1N0 + a2N0T- a3/N0)/T]
Temperature dependence of Gain and Transparency
G(T) = G0(ag0+ ag1T +ag2T2) / (bg0+ bg1T +bg2T
2)
N0(T) = Nt0(cn0+cn1T+cn2T2)
Transim Power vs Current
0.00E+00
5.00E-04
1.00E-03
1.50E-03
2.00E-03
2.50E-03
3.00E-03
3.50E-03
0 0.005 0.01 0.015 0.02 0.025 0.03 0.035
Current(amps)
Power(watts)
Power@298K
Power@323K
Power@338K
Leakage @298K
Leakage(mA)
0
10
20
30
Transient Optical Output
Power
Time(10ns)
drive current
Time(ns)
Wavelength Chirp
DC Optical Power versus Drive Current
Rollover from leakage
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Power and Wavelength degradation due to two components
Electro-Optics
Optical PowerWavelength
z=12m z=12m
m
f1=12mm, R=0.04 f2=12mm, R=0.04
Detector
Lens2Lens
1
Vcsel
No feedback
L1 feedback
L1+L2 feedback
No feedback
L1 feedback
L1+L2 feedback
Output power
degradation due
to single and
double lens feedback
Output wavelength
degradation due
to single and
double lens feedback
With:
Mark Niefeld
Ravi Pant
Univ. of Arizona
Feedback Results:
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Time Delays
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Spice handles only short (< 4 time step) time delays.
TWTA used to validated fREEDAs
ability to handle models with long
time delays. Also implemented in
many transistor models.
100
101
102
103
104
100
101
102
103
104
Specified delay (ns)
Observeddelay(ns)
0 2000 4000 6000 8000 10000 12000 14000
-1
-0.5
0
0.5
1
Time (ps)
InputTerminalVoltage(volts)
0 2000 4000 6000 8000 10000 12000 14000-3
-2
-1
0
1
2
3
Time (ps)
OutputTerminalVoltage(volts)
fREEDA has no limit
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Choice of Time Step to keep error below a set tolerance.
Conventional
approachResult obtained
with linear
extrapolation
Result from
nonlinear
iteration
(Trapezoidal /
Backward
Euler)
Tn+1TnTn-1
Error
estimate
Poor estimate of error leads to
inappropriate choice of time step
ConventionalTime Stepping Algorithm
IDEAL
RESULT
The difference between
the nonlinear iteration and
the straight line extrapolation is
taken as an estimate of error.
If the error is too large the
time step is reduced bya factor of 2.
If the error is very low the
time step is increased by
A factor of 2.
This results in excessively
short time steps around curves
and limits dynamic range.
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fREEDA Time Stepping Algorithm
New
approach
Error
estimate
Tn+1TnTn-1
Better estimate of error leads to
a better choice of time step
Result from
Backward Euler
Result from trapezoidalIDEAL
RESULT
The difference between
the Backward Euler and
trapezoidal estimates is
an incredibly good estimate
of error. If the error is too
large the time step isreduced by a factor of 2.
If the error is very low the
time step is increased by
A factor of 2.
The half way point is
taken as the answer.
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0
Tolerance
0.002 0.004 0.006 0.008 0.01
Error
0.01
0.02
0
0.03
0.04
0.05
CONVENTIONAL
NEW
High Dynamic Range
Through Error Control
The new approachis a better
estimate of error.
Better time point
selection.
160 dBc
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fREEDA, Transient Simulation
and Frequency-DomainModeling
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Three Milestones for Interfacing EM and
Circuits
D. Winkelstein, M. B. Steer, and R. Pomerleau, Simulation of arbitrary transmiss ion line networks w ith nonlinear
terminations, IEEE Trans. on Circui ts and Systems, April 1991, pp.418-422. See also, IEEE Trans. on Circui ts and
Systems, Vol. 38, Oct. 1991.
Impulse response and convolut ion
Time and f requency bounded
C. S. Saunders, J. Hu, C. E. Christoffersen, and M. B. Steer, Inverse singu lar value method for enforc ing passivi ty
in reduced-order models of distribu ted structures for transient and steady-state simulation, IEEE Trans.
Microwave Theory and Techniques, April 2011, pp. 837847.
S parameters to Foster Model
Passivity, causality
C. S. Saunders and M. B. Steer, Passivity enforcement for admittance models of distributed networks using an
inverse eigenvalue method, IEEE Transactions on Microwave Theory and Techniques, In Press.
y parameters to Foster Model
Passivity, causality What is needed for ci rcuit s imualtpors which are y parameter based
ALL CONVERTERS NEED SOME HUERITIC KNOWLEDGE
Did the user provide sufficient data
If not how to extrapolate
What i s the basic response (what to emphasize)
Low pass, Bandpass
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http://wolftech.ad.ncsu.edu/ece/centers/muri_mbs/mbs%20CV/Publications/vitae_papers/X2010/saunders_hu_singular_2010.pdfhttp://wolftech.ad.ncsu.edu/ece/centers/muri_mbs/mbs%20CV/Publications/vitae_papers/X2010/saunders_hu_singular_2010.pdf -
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SINCGARS
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Output Waveforms
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Summary
Most robust circuit simulator technology
Interfaces with TD and FD EM solvers.
Will be supported commercially.
fREEDA papers athttp://people.engr.ncsu.edu/mbs/Publications/mbs_publications.html
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http://people.engr.ncsu.edu/mbs/Publications/mbs_publications.htmlhttp://people.engr.ncsu.edu/mbs/Publications/mbs_publications.html