sribasta bidyadhar conf
TRANSCRIPT
Fuzzy Logic Controller-based High Performance Induction Motor Drive
S. Behera B. Subudhi S.P.Das & S.R.Doradla UCE, Burla IGIT, Sarang IIT Kanpur
Abstract: A Fuzzy Logic Controller (FLC) is proposed for high performance induction motor drive. The d-q model of the complete scheme is formulated and analyzed by MATLAB simulator with FLC. Later, the scheme is implemented on a laboratory-sized experimental setup. The simulation and experiment are carried out under identical operating conditions and presented. The comparison of simulation and experimental results under identical operating conditions reveals good agreement.
Keywords:- Fuzzy Logic Controller, MATLAB simulation, and Direct torque control (DTC) Scheme
I. INTRODUCTION
Commencing from domestic appliances to
industries, the induction motors are widely used
because of their simplicity, ruggedness and
robustness. The operational schemes of variable
voltage and variable frequency are generally
used for speed and torque control of induction
motor drives. The literature related to ac drives
covering scalar control, field-oriented control,
and direct-torque control (DTC) has been well
documented [1-5]. In all these schemes, a better
torque profile and current response have been
focused. The conventional proportional-integral
controller (PI), which acts as one of the major
part of these controlling processes, plays crucial
role during mathematical modeling and
implementation. These PI controllers have got
certain limitations. It has no reach to the systems,
which are quite complex and the mathematical
models are not available. In such a situations,
Fuzzy Logic has much importance to act. Fuzzy
Logic [5,6] has emerged as one of the active
areas of research particularly in control
applications. Whenever a logic in the spirit of
human thinking can be introduced, Fuzzy Logic
controller (FLC) finds reliable applications there.
The applications of FLC to vector oriented
controlled induction motor have been
documented [8,9]. In this paper, the application
of fuzzy logic controller in field of high
performance drives has been illustrated with
some prominent simulation and experimental
results. Typical performance results under a step
change of load torque and speed reversal for both
simulation and implementation are presented and
are seen to be in good agreement.
II. FUZZY LOGIC CONTROLLER IN DRIVES
In most dc/ac drives, speed regulation is
required with certain precisions. Obviously these
types of systems operate on close-loop basis
which constitute mostly different sensors (speed,
voltage, current), control blocks (i.e.,
analog/digital) and the power-handling unit. The
performance of the system in terms of their
control system parameters (i.e., settling time,
rising time, overshoot) mostly depends upon the
electrical, mechanical time constants of the
drives and the type of control techniques
employed. When the motor in such a drive is of
high inertia and low electrical time constant, the
transient performance such as speed is not up to
expectation with conventional PI controller.
With PID (proportional-integral-derivative)
controller, though the transient performance can
be improved slightly, but it is still far beyond the
expected one. In such a case, fuzzy logic
controller can be utilized for improvements of
both transient and steady state performances. The
fuzzy logic control approach for dc/ac motor
drive systems is very useful since exact
mathematical model of it is not required. The
function of fuzzy logic controller is to transform
linguistic rules into control strategy based on
expert knowledge.
The fuzzy logic control system (Fig.1) can
be divided into four main functional blocks
namely Knowledge base, Fuzzification, Inference
mechanism and Defuzzification. The knowledge
base is composed of data-base and rule-base. The
data-base, consisting of input and output
membership functions, provides information for
appropriate fuzzification operations, the
inference mechanism and defuzzification. The
rule-base consists of a set of linguistic rules
relating the fuzzy input variables to the desired
control actions. Fuzzification converts a crisp
input signal, the error (e), and error change (∆e)
into fuzzified signals that can be identified by
level of membership in the fuzzy sets. The
inference mechanism uses the collection of
linguistic rules to convert the input conditions to
fuzzified output. Finally, the defuzzification
converts the fuzzy outputs to crisp control
signals, which in the system acts as the changes
in the control input that finally drives the motor.
This control input may be change in torque, flux,
or speed component. The typical input
membership functions for speed error and
change in speed error are shown in Fig. 2 and
Fig. 3 respectively, whereas the output
membership function for change in control input
is shown in Fig. 4. The output generated by
fuzzy controller must be crisp which is used to
control the drive unit and this is accomplished
by the defuzzification block. Knowledge base
involves defining the rules represented as a set of
if then rules, for example if speed error is
positive large ‘PL’ and error change is negative
large ‘NL’, then change in output is zero ‘Z’.
The control rules are evaluated by inference
mechanism. Various fuzzy control rules are
shown in [6,7]. Many defuzzification strategies
are available [6], such as, the weight-average
criterion, the mean-max membership, and center-
of-area (centroid) method. The defuzzification
technique using centroid method is summarized
as follows and shown in Fig. 5. Suppose the
speed error is –20 and change in speed error is -
17, then e will be NS and the change in error will
be PS or PL. So the rules relating the error and
error rate are :-
If ‘e’ is ‘NS’ and ‘de’ is ‘PS’ then change in
control input is ‘Z’ (Fig. 5(a)).
If ‘e’ is ‘NS’ and ‘de’ is ‘PL’ then change in
control input is ‘PS’ (Fig. 5(b))
By using the most commonly used
defuzzification method, i.e. the Center-of-area
method, the defuzzified values of increment in
control inputs are obtained as
C* = (C1 * A1 + C2 * A2)/ (A1+A2)
where C1, A1: - Centroid and area derived
(i.e., from Fig. 5(a)) from membership function
for change in control input. Similarly, C2 and A2
represent centroid and area shown in Fig. 5(b).
III. HARDWARE IMPLEMENTATION.
The hardware implementation of the proposed
scheme has been shown in Fig. 6. The hardware
section comprises IGBT drivers for inverter,
current sensors, voltage sensor, and a tacho-
generator coupled with induction motor-dc
generator set. The data-acquisition card used is
ACL-8112PG and it has been attached to a PC
having Pentium- IV CPU. PI-type FLC replaces
the conventional PI controller. The control
strategies of conventional DTC scheme are given
in [1-3].
IV. SIMULATION AND EXPERIMENTAL RESULTS
The FLC-based DTC scheme incorporating
the inverter is modeled and analyzed in
MATLAB simulator. The input dc voltage is 120
V. The simulation is carried out to observe
various responses for step changes in speed, load
torque. Typical simulation results are given in
Figs. 7-10.
Figure 7 shows the response of speed with
conventional PI and PI-type FLC under both
forward and reverse directions. It is observed that
performance with PI-type FLC is better than
conventional controller. In Figs.8-10, both
simulations and experimental results of FLC-
based DTC scheme were presented for different
conditions. Fig.8 and Fig.9 show the responses of
stator flux and speed respectively from rest with
and without load torque. It may be noted that
both stator flux and rotor speed are unaffected
when a load torque of 1 N-m is subjected for a
small interval. The responses of speed and flux
from both simulation and experiment during four-
quadrant operation for a reference speed of 500
rpm are shown in Fig. 10. It may be noted that
response of flux is undisturbed during four-
quadrant operation.
V. CONCLUSION
The PI-type FLC has been successfully
implemented in a direct torque controlled
induction machine. The complete setup has been
analyzed with MATLAB simulator. The transient
and steady state responses from FLC-based DTC
scheme have shown good agreement between
simulation and experimental results. The
performance of the given drive indicates that such
controller will find wide range of application in
ac drives [8, 9] as far as automation is concerned
due to better performance, high reliability,
robustness and cheapness.
REFERENCES
[1] I. Takashashi and T. Nouguchi, “A new quick-response and high-efficiency control strategy of an induction motor,” IEEE Trans on Industry Applications, vol. IA.22, no. 5, pp. 820-827, Sep/Oct - 1986.
[2] M. Depenbrock, “Direct self-control (DSC) of inverter-fed induction machine,” IEEE Trans on Power Electronics, vol. 3, no. 4, pp. 420-429, Oct- 1988.
[3] J.N. Nash, “Direct torque control, induction motor vector control without encoder,” IEEE Trans on Ind. Appl., vol. 33, no. 2, pp. 333-341, Mar/Apr- 1997.
[4] B.K. Bose, “High performance control of induction motor drives,” IEEE Industrial Electronics Society Newsletter, pp. 7-11, Sep-1998.
[5] S. Behera, S. P. Das and S. R. Doradla, “A novel quasi-resonant inverter for high performance induction motor
drives” IEEE APEC Conference Rec.-2003, vol-2, pp 819- 825. (i.e., Miami, USA)
[6] T.J.Ross, “Fuzzy Logic with Engineering Applications”, Mc Graw-Hill Publications, International Edition, 1997
[7] I.J.Nagrath and M. Gopal, “A Text Book of Control System Engineering”, New Age International Publication, New Edition, 2003
[8] G. C. D. Sousa, B. K. Bose and J. G. Cleland, “Fuzzy logic based on line efficiency optimization control of an indirect vector controlled induction mpotor drive”, IEEE Trans. Ind. Electronics., vol. 42, No .2, pp. 192-198, Apr 1995.
[9] E. Cerruto, A.Consoli, A. Raciti, and A. Testa, “Fuzzy adaptive vector control of induction motor drives,” IEEE Trans. Power Electronics, vol. 12, No. 6, pp. 1028-1039, Nov 1997.
Knowledge Base
Data base Rule basespeed error
e
input ∆u
error change ∆e
Fuzzification Defuzzification Inference Mechanisim
Fig. 1. Functional block diagram of fuzzy logic control
NL PLPSNS 1Z
-40 -30 -20 0 20 30 40
NL PLPSNS 1Z
0 15 50 90-15-50-90∆u ------
Fig.4. Memberhip function for change in control input
e ----- Fig.2. Memberhip function for speed error
NS PS Z
-20 17
C1, A1
NS PL PS
-20 17
C2, A2
NS PS PL1
ZNL
-20 -15 -5 0 5 15 20
(a)
∆e ----- Fig.3. Memberhip function for change in
speed error (b)
Fig. 5. Defuzzificztion technique using centeroid method
FLC
Opt
imum
Switc
hing
Tabl
e
Filter &Amplifier
ψs
ψs*
Te*Nref
N
Te
Sa
ia
Vdc
D-Q-Model
3-Ph
ase
Inve
rter
IM
Sc
Sc
Vdc
ibic
Sb
Sa Sb
Personal Computer (PC)
LIMITER
Two Level HystresisController
Three Level HystresisController
DCG
TG
Sectorstatus
Fig. 6: Hardware Implementation of FLC-based DTC Scheme
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.3 1.4-60 -50 -40 -30 -20 -10
0 10 20 30 40 50 60
time(sec)
(a) (b) Fig.7. Speed response during when forward and reversal direction
(a) PI controller (b) PI-type FLC Scale: 1:10
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.3
60
50
40
30
20
1.4-60
-50
-40
-30
-20
-10
0
10
Speed
time(sec)
0 0.5 1 1.5 2 2.5 3 3.50
1
2
3
4
0 0.5 1 1.5 2 2.5 3 3.50
1
2
3
4
0 0.5 1 1.5 2 2.5 3 3.50
1
2
3
4
0 0.5 1 1.5 2 2.5 3 3.50
200
400
600
800
1000
1200
Rotor speed (rpm)
Load Torque (N-m)
(a)
Ψs, (Wb)
Load Torque (N-m)
(a)
Nr, (rpm)
(Scale: 1000 rpm / 6 V)
Load
Torque (N-m))
(b) Fig. 9. Speed (Nr) responses during step change in reference speed from 0 to 500 rpm and a load torque of 1 N-m is applied by closing load switch for 1 sec. (GLoad – gate pulse of load switch)
(a) Simulation (b) Experimental scale: 1:1 scale: 1:1
Ψs, (Wb)
Load Torque (N-m)
(b) Fig. 8. Flux (Ψs) responses during step change in reference speed from 0 to 500 rpm and a load torque of 1 N-m is applied by closing load switch for 1 sec.
(GLoad – gate pulse of load switch) (a) Simulation (b) Experimental scale: 1:1 scale: 1Wb/5V, 1 N-m/5V
Nr,(rpm)
Ψs,(Wb)
0 0.5 1 1.5 2 2.5 3 3.5-1000
-500
0
500
1000
0 0.5 1 1.5 2 2.5 3 3.50
1
2
3
(a) (b) Fig. 10. Responses of rotor speed (Nr) and stator flux (Ψs) during speed reversal command in reference speed (a) Simulation Result (b) Experimental Scale: 1:1 (Scale: 1000 rpm/ 6V for Nr and 1 Wb/ 5V for Ψs)