(from ibm) low power issues in chip design
TRANSCRIPT
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ICCAD 03
Leakage Issues in IC Design: Part 3
Anirudh Devgan
IBM Research Austin
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utline
Part1: Siva Narendra (Intel Corporation)
Device physics, process technology, leakage fundamentals
Part 2: David Blaauw (University of Michigan)
MTCMOS, Dual-Vt, estimation/optimization techniques for dual-Vt
Part3: Anirudh Devgan (IBM Corporation)
Process & Environmental variations, ABB, Vdd control
Part4: Farid Najm (University of Toronto) State dependence, sleep states, memory/cache circuits and architectures
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eakage
Leakage power is becoming asignificant portion of total power.
Currently managed to 15-20% in
current IBM designs.
Expected to increase dramatically infuture designs & technologies.
In some cases (11S), predicted to
more than 50% of total power.
Leakage is the problem Emerging as the critical challenge in
VLSI Design.
Leakage depends super linearly with
Process variations, Temperature,Power supply voltage
Gate
S
ub-Threshol
d
1.E+00
1.E+01
1.E+02
1.E+03
1.E+04
1990 1995 2000 2005 2010 2015 2
NTRS '97
ITRS '99
ITRS '01
International Technology Roadma
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ariability: Leakage and Timing
Source: Intel, DAC 2003
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eakage & Thermal Variations
L3Directory/Control
L 2 L 2 L 2
L S U L S UIF UB X U
ID U ID U
IF UB X U
F P U F P UFXU
FXUIS U IS U
Temperature varies with-in the chip
Chip Floorplan Chip Thermal Profile
Power 4 Server Chip: 2 CPU on a chip
The CPUs can be much hotter than the caches
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ower Supply Variations
Vcrit
time
Voltage
VDD+
Rg
Rd
Cd
L
Package Grid
Decap Load
IDD
time
tp
LoadWaveform
DC Decap Package
~SameVDD Noise l tp Rg + L R2g Cd (1 e
-tp/)
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ower Delivery
onnection
package
Connection to circuits
C4 balls
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upply Voltage & Temperature
Leakage dependence on Vdd
Variation in both gate and sub-threshold leakage.
Need to combine Power supply
analysis with Leakage.
Leakage significantly affected by
temperature. With-in die temperature variations
need to be modeled.
0
0.5
1
1.5
2
2.5
3
0.6 0.7 0.8 0.9 1 1.1 1.2
Gate Subthreshold Sum
0
0.01
0.02
0.03
0.04
0.05
0.06
0.07
0.08
0.09
0.1
55 70 85 100 115
Temperature (deg C)
M ean LeakageM ax Leakage
M in Leakage
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Power integrity & Package
Package design becoming increasingly complicated Large number of power/ground layers in current packages
Significant Power supply variations caused by the package
chipcapacitorcapacitor
chip carrier
Solder balls
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ower Supply Variations Package Effects
C4s
Balls
lanes
VDD
GND
Power IR Drop by the package
Is usually non- uniform across the various
C4
Can be difficult to predict and analyze
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Variability Real?
S. Nassif DAC 2003
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ariability Time Scales
10 10-8 10-7 10-5 10-4 10-2 105 107
Risin
g/R
isin
g
Risin
g/F
alli
ng
nal Coupling SOI History
VDD/Package Noise
Temperature Process Line
S. Nassif DAC 200
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ariability Distribution
Physical: Die to die variation
Imposedupon the design (constant regardless of design).
Well modeled via worst-case files. Within-die variation
Co-generatedbetween design and process (depends on details ofthe design).
Example: nested vs. isolated poly-silicon L.
Environmental:
Only makes sense within-die.
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ariability vs. Uncertainty
Variability: known quantitative relationship to a source(readily modeled and simulated).
Designer has option to nullout impact.
Example: power grid noise.
Uncertainty: sources unknown, or model too difficult/costly to
generate or simulate.
Usually treated by some type of worst-case analysis.
Example: L within die variation.
Lack of modeling resources often transforms variability toLack of modeling resources often transforms variability to
uncertainty.uncertainty. Example: nearest neighbor noise coupling.Example: nearest neighbor noise coupling.
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ithin-Die Variations?
Fundamentally different from die-to-die. Environmental components:
VDD & Temperature variations are natural byproducts of power
distribution analysis. Power distribution analysis unavoidable .
Physical components:
VT and L variations across the die. Lot, Wafer, and Die distributions.
Layout (design) dependent.
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patial Variability
Die 1 Die 2
wafe
Param
eter
Posit
Facility, Line, Lot, Wafer &Die components.
Semi-periodic across wafer.
Wafer level and above arenot of interest to a designer.
Designer does not get to chooseDesigner does not get to choose
where on a wafer his design goes!where on a wafer his design goes!
S. Nassif DAC 2003
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ources of Within-Die Variations
Poly line-width (LEFF
) variation comes from:
Mask, Exposure and Etch variations
Essentially identical to modeling required for OPC.
Mask & OPC biasMask & OPC bias
ResistResistPolyPoly
SiliconSilicon
Layout (designer view)
Lithography biasLithography bias
Etch biasEtch bias
S. Nassif DAC 2003
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EFF variations via OPC
S. Nassif DAC 2003
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ources of Within-Die Variations
Vertical variations are caused by chemical-mechanical
planarization (CMP) process.
polishes
faster
C1 C2
S. Nassif DAC 2003
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eakage Modeling and Analysis
Gate
Sub-Th
reshold
Input pattern vector(state)
Process Variations
(L, VT, TOX, )
Operating Environment(Temperature, VDD, )
Topology
All effects need to be accurately modeled
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Leakage Requirements
Need to include environmental and process variation
Channel lengthSupply voltage
Temperature
Standby leakage
Active & burn-in leakage
S. Narendra ICCAD 20
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rocess Dependence
Leakage varies exponentially with process variations.
10X variation due to process vs. 10% variations due to different patterns.
Reason: sub-threshold current varies exponentially with process variations
0
0.05
0.1
0.15
0.2
0.25
1 2 3 4 5
Process Variation Parameter (NRN)
Leakage(mA)
M in Leakage
M ean Leakage
M ax Leakage
~10%
~10X IDDQ for typical chip
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eakage & Process Variations
Process parameters (Leff, Vth) have great influence
Generate leakage performance statistics
Practical bounds for a given confidence level can be driven
Cumulative
Distribution for
Leakage
Within-chip(Deterministic)
Global variationsL
eff
distribution
Within-chip(Random)
+ +
Total Leakage
0.99
L3
=L0.99L-3 =L0.01
0.01
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rocess Variations
Leakage is exponentially dependent on process variations
eII omeanLL
=
)(
Normal distribution of L leads to a LogNormal distribution of leakage.
S. Narendra ICCAD 2
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rocess Variations: ACLV
-4 -3 -2 -1 0 1 2 3 4Global Sigma
NoofChip
s
-4 -3 -2 -1 0 1 2 3 4
ACLV Sigma
0.0
0.2
0.4
0.6
0.8
1.0
1.2
NoofTransistors
Chip
Mean
Leff
With-in Chip:ACLV
Chip to Chip Variation
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Leakage modeling
o
n
n
no
p
p
p
l-leak I
k
wI
k
wI +=
Lower bound:
Assumes all devices in the die are nominal L
3
noffn
n3
poffp
p
u-leak
Ik
wI
k
wI
+
=
Upper bound:
Assumes all devices in the die are minimum L
Prior techniques
S. Narendra ICCAD 20
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Applications
=
o
leak
I
I
w
kln2
A macroscopic standard
deviation () representing
parameter variation in a chip
2
n
2
2n
n
non
2p2
2p
p
pop
wleak ek
wI
ek
wI
+= Leakageestimation
Depends on parameters that can be estimatedS. Narendra ICCAD 2002
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Measurement results0.18 um 32-bit microprocessors (n=960)
0
100
200
300
400
500
0.1 1 10 100
Ratio of measured to
calculated leakage
Nu
mberofsamples
: 0.65: 0.27
: 6.5 : 3.8
Ileak-l
Ileak-u
: 1.04 : 0.3Ileak-w
0
100
200
300
400
500
0.1 1 10 100
Ratio of measured to
calculated leakage
Nu
mberofsamples
: 0.65: 0.27
: 6.5 : 3.8
Ileak-l
Ileak-u
: 1.04 : 0.3Ileak-w
50% of the samples within 20% of the measured leakage
Compared 11% and 0.2% of the samples using other techniques
S. Narendra ICCAD 200
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haracterizing the variation
Variations in channel length occur at both the intra-die (within-die) level and
inter-die (die-to-die) level
iintra,internominalitotal LLLL ++=,
Lintra
Linter
R. Rao,et al. ISLPED 200
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mpirical Model
Using the following mathematical model
Eliminate Vth as an intermediate variable and use general form of SPICE modelto perform empirical fitting on channel length
Properties of this equation: Preserves exponential dependency of Ion L
Is easily invertible (simple quadratic equation formula)
Yields closed-form expressions for the PDF of I
Accurately fits over a wide range of values of L for NMOS/PMOS and transistor stacks
( ) ( )== + LheqI dd LqLq2
32
1
( )IgIqqqq
qL =
+
= 13222
3
ln421
R. Rao,et al. ISLPED 2003
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oodness of fit
NMOS in 0.18m: Vgs=0, Vds=Vdd and 10% variation in Ld
Comparison of simulation datawith analytical expression
Comparison of experimental PDFwith PDF obtained analytically
SimulationAnalytical
BSIM3 Fit
SimulationAnalytical
R. Rao,et al. ISLPED 200
f /
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ccounting for inter/intra-die variations
We accommodate variation across both levels in our empirical
model
Assume L,total=15%. First determine the parameters for L,inter=0% and
L,intra=15% of nominal
Enumerate all inter-die variation points (Ex: 1%, 2% etc.,)
For each point, shift the mean by L,interand obtain the distribution of currents
around that average point using L,intra Perform weighted summation across the range of L,inter
iintra,internominalitotal
LLLL ++=,
222
intraL,interL,totalL, +=
WeightedSummation
R. Rao,et al. ISLPED
k PDF f diff t i t /i t di i ti
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eakage PDF for different intra/inter-die variation
R. Rao,et al. ISLPED 200
k M d li d A l i
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eakage Modeling and Analysis
Gate
Sub-Th
reshold
Input pattern vector(state)
Process Variations
(L, VT, TOX, )
Operating Environment(Temperature, VDD, )
Topology
All effects need to be accurately modeled
ith hi i t l i ti
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ower with on-chip environmental variations
Leakagepower(P0)
Dynamicpower(PD0)
Converge ?Stop
Thermalprofile
Voltage dropcontour
Leakage ModelPleak= P0f(dVdd, dT)
Dynamic powermodel ~ dVdd
2
N
Y
h l P fil C t ti
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hermal Profile Computation
Full chip thermal model
Thermal system modeled is this paper is assumed to be static (i.e. not time-varying) Dynamic, time varying model can also be used if desired
Silicon
Substrate
SiO2
Si
Metal +
ILD
C4
Heat sinks
Package
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Thermal Equations
0),,(),,(2 =+ zyxpzyxTk
Steady-state heat conduction equation:
wherep is the power density of the heat sources, kis the thermal conductivity
Boundary conditions
Isothermal (Dirichlet): T = fi(x,y,z)
insulated (Neumann): T/ ni
= 0
Convective (Robin): ki T/ ni=hi(T Ta)
h l M d l
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hermal Model
dxdydz
p
dz
TTT
dy
TTT
dx
TTT zyxzyxzyxzyxzyxzyxzyxzyxzyx
k =++ +++++ +++
)( 21,,,,1,,
2
,1,,,,1,
2
,,1,,,,1 222
kdydzdx
iR =
Tx,y,z Tx+1,y,zTx-1,y,z
Tx,y+1,z
Tx,y-1,z
Tx,y,z+1
Tx,y,z-1
Thermal network
Model the circuit as a linear circuit
hdydzbR 1=
h l M d l
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hermal Model
Analogy between thermal and electrical circuits:Thermal Electrical
T : Temperature (K) == V
Rh: Thermal res (K/W) == RQ : Heat flow (W) == I
Thermal System can be modeled as linear circuit
GV=I
However, thermal modeling of a typical chip leads to millions of nodes
Need to use specialized linear solvers
i it A l i f Th l/VDD i it
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ircuit Analysis for Thermal/VDD circuits
General equation: Gx + Cx = B(t)
G conductance matrix.
Ccapacitance matrix.
x, x nodes voltages & KVL currents, time derivative.
B(t) time dependent current sources.
Analysis using SPICE-like simulators is not practical. Dimension ofx~ 105 to 107.
Standard circuit simulators cannot make use of any special properties of the
analysis.
l i A l ti
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nalysis Acceleration
Make use of the linearity.
BE discretization: (G+C/h)x(t+h) = B(t)+(C/h)x(t).
System Solution:x(t+h) = (B(t)+(C/h)x(t))(G+C/h)1.
The matrix (G+C/h) is independent of time only needs to be inverted once.
Avoid data explosion.
One layout polygon translates to many resistors.
Retain geometrical description and leverage to reduce translation overhead.
Specialized Linear Solvers.
Algebraic multi-grid (AMG) solvers
lti G id M th d
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ulti-Grid MethodsBasic idea:
Reduce original grid h to a coarser grid 2h. Map problem from original to coarser grid.
Solve problem at coarse grid (iterative solver).
Map solution back to fine grid and refine.
Systems:
Fine:Ahxh= bh Coarse: A2hx2h= b2h
Fine Coarse
eakage Variation
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eakage Variation
1.159-1.2
1.016-1.196
Vdd (V)
-0.13675.5 89.11.122
-1.85080.8 110.39.601
Change in
Leakage
withvariations
(W)
T (C)Leakage
(No
variations)(W)
Chip
hermal & Power Grid Solver
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hermal & Power Grid Solver
Power Grid
Power Grid
Power Grid
Thermal
Thermal
Analysis
2.1438.102.73M
1.3293.581.74M
0.4688.39630k
0.61139.17270k
0.4582.13170k
Mem (GB)Runtime
(sec)
Matrix Size
eakage Modeling
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eakage Modeling
Leakage various super linearly with temperature and power supply voltageHowever, on chip variations of temperature and voltage are limited
Leakage as a function of temperature and voltage is modeled as second order
]
1)[0,0(),(
1
2
21
2
21
VTcVbVb
TaTaITVI
+++
++=
Gate and subthreshold leakage is modeled separately
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esults: Thermal profile
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esults: Thermal profile
Thermal map of 9mm x 9mm ASIC chip
esults: VDD Profile
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esults: VDD Profile
VDD profile
esults: Leakage w/ VDD & Temp Variations
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esults: Leakage w/ VDD & Temp Variations
Leakage considering environmental variations
Accurate leakage model of actual VDD and temperature profile
For this example, leakage is lower by 10%
omparison to Fixed Drop Analysis
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omparison to Fixed Drop Analysis
Need to accurately captures the on-chip locality of power supplyand temperature and their influence on leakage
Reduce the optimism of the fixeddrop method
85
80.8 -
110.3
T (C)
-4.295.311.08Fixed
Drop
-1.857.751.016-
1.196
OCV
Change in
Leakage(W)
Leakag
e(W)
Vdd (V)Chip 1
i bl Th h ld CMOS (VTCMOS)
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ariable Threshold CMOS (VTCMOS)
Body effect to change device Vt Standby leakage reduction with maximum reverse bias Triple well structure
N-isolation
P-sub
N-well P-well
VBBP VDD VSS VBBN
p+ p+ n+ n+
VDD
VSS
VBBP
VBBN
BBBBt0t 2V2VV +=
Body Effect:
TCMOS
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TCMOS
Variable Threshold CMOS (from T. Kuroda, ISSCC, 1996) In active mode:
Zero or slightly forward body biasfor high speed
In standby mode:
Deep reverse body bias for lowleakage
Triple well technology required
Kaushik Roy, ECE, Purdue University
VTCMOS Example
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C OS a p e
T. Kuroda, et al, A 0.9V, 150Mhz, 10mW, 4mm2, 2-DCT CProcessor with Variable Vt Scheme, JSSC Nov. 1996
VTCMOS principle applied to 4-mDCT core processor
SSB increases Vt (more reversebias)
SCI decreases Vt (Standby -> Sle Leakage reduction
0.1mA active -> 10nA sleep (2.8v V
4 orders of magnitude
Dynamically tunes Vt(by matchin
leakage current monitor) tominimize Vt variation
J Kao ICCAD 2002
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VTCMOS Pros/Cons
PROS: Significant standby leakage reduction Memory elements retain state
No transistor sizing/ partitioning required Dynamically tunable Vt during runtime
CONS:
Requires expensive triple well process Body factor decreases with scaling
J Kao ICCAD 200
DVS vs DVTS
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TSMC 250 nm BPTM 70nm( Vdd=2.5V, Vth=0.45V ) ( Vdd=0.9V, Vth=0.15V )
DVS vs. DVTS
ushik Roy, ECE, Purdue University
Speed Adaptive V CMOS
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Speed Adaptive Vt CMOS
M. Miyazaki, et al, A 1.2-GIPS/W uProc Using Sp
Adapative Vt CMOS with Forward Bias, JSSC Fe2002.
Dynamically tune Vt so that critical pathspeed matched clock period
Reduces chip-to-chip parameter variation
Reverse bias:Operate only as fast as necessary (reduces ex
active leakage)
Forward bias:
Speeds up slow chips
Standby leakage with maximum reverse bi Also known as Adaptive Body Biasing (A
J Kao ICCAD 200
Adaptive Supply & Body Bias (ASB)
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0
0.1
0.2
0.3
0.1 0.3 0.5 0.7 0.9
VDD [Volts]
P
ower[Watts
]
Ptotal
Pdynamic
Pleakage
Minimum point where
slope(leak) = - slope(dyn)
Power vs. VDD (implicit Vt) for fixed frequency
Dynamically tune both VDD & Vt as operating conditions change Trade-off between dynamic power (VDD knob), leakage power (Vt)
Minimize total ACTIVE power consumption
(higher active leakage current at expense of lowering dynamic power)
Adaptive Supply & Body Bias (ASB)
M. Miyazaki, et al, A 175mV Multiply-Accumulate Unit using an AdaptiveSupply Voltage and Body Bias (ASB)Architecture, ISSCC February 2002.
J Kao ICCAD 2002
Optimal VDD/VT Selection
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0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1
0.1 0.6 1.1 1.6 2.1
VDD [Volts]
Vt[Volts]
50 Mhz100 Mhz
150 Mhz
200 Mhz
250 Mhz
Vt-VDD Constant Performance Locus
0
0.5
1
1.5
2
2.5
3
0.1 0.6 1.1 1.6 2.1
VDD [Volts]
Power[Watts]
50 Mhz
100 Mhz150 Mhz
200 Mhz
250 Mhz
Minimum Power Point (Vt implicit)
Optimal VDD
& Vt
target changes with operating conditions
e.g. Varying Workload
Low frequencies high Vt more optimal
reduce leakage at expense of increased dynamic
High Frequencies low VDD more optimal
reduce dynamic at expense of increased leakage
Optimal VDD/VT Selection
J Kao ICCAD 200
V /V Optimi ation s DVS
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0
0.5
1
1.5
2
2.5
3
0 50 100 150 200 250
Frequency [Mhz]
Power[Watts]
DVS (Vt=0.35)
DVS (Vt=0.14)
Optimal VDD/Vt Scaling
0
0.05
0.1
0.15
0.2
0.25
0 50 100 150
Fre quency [M hz]
Power[Watts]
DVS (Vt=0.35)DVS (Vt=0.14)
Optimal VDD/V tScaling
VDD/VT Optimization vs. DVS
Dynamic voltage scaling ignores VT influence DVS is sub-optimal over the frequency range
J Kao ICCAD 200
ASB A hit t
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Variable
DC/DC ABB Generator
DSPCORE
VDD
VBBN
Powermonitor
Controller Vt Controller
ASB Architecture
VBBP
Decouple VDD/ Vt tuning loops
ABB (Auto Body Biasing)generator chooses Vt based onVDD/ Freq/ etc.
Simple VDD sweep to searchminimum active power point
Architecture ensures minimumpower for any operatingcondition
M. Miyazaki, J. Kao, A. Chandrakasan, A 175mV Multiply-Accumulate Unit using an Adaptive SupplyVoltage and Body Bias (ASB) Architecture, ISSCC February 2002.
J Kao ICCAD 20
ctive Well vs VDD Scaling
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ct e e s Sca g
Reverse Body bias (Active Well) is a more effective leakage minimization technique
than VDD scaling
Total Power savings depends on ratio of leakage to total power
Vdd scaling reduces dynamic power much more than Active Well
Leakage Power (for 65nm) Total Power (for 65nm)
B. Chatterjee, et al ISLPED 2003
ackground: Active Well vs VDD Scaling
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ackground: Active Well vs VDD Scaling
VDD scaling
Less effective than Active Well to reduce leakage
Causes higher degradation in performance
More effective in reducing dynamic power
Active Well
More effective in reducing leakage
Does not work with SOI
Effectiveness reducing in newer technologies but still more effective than VDD scaling till 65
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otal Power and VDD Scaling
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otal Power and VDD Scaling
Total Power (for 65nm)Total Power (for 130nm)
VDD scaling is very effective in current technologies to reduce dynamic power
VDD scaling is more attractive if total power is dominated by dynamic power.
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Vth hopping scheme (Variable Vth)
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Vth hopping scheme (Variable Vth)
K. Nose, JSSC 02Kaushik Roy, ECE, Purdue University
Vth hopping scheme
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K. Nose, JSSC 02
Vth hopping scheme
aushik Roy, ECE, Purdue University
he DVTS Scheme
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he DVTS Scheme
Frequency
PMOS
body bias
NMOS
ody bias
Vth
Fmax
0.9 V
2.7 V
-1.8 V
0
0.15 V
0.45 V
time
Kaushik Roy, ECE, Purdue University
Implementation overview
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Implementation overview
Schematic of the DVTS system
Charge PumpsFeedback Alg.
VCON
Counter
+
-Counter
CLK
+
SystemPMOS body bias
NMOS body bias
error[n] = Fclock[n] Fvco[n]
Kaushik Roy, ECE, Purdue University
Forward Body-Biasing (50nm)
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Previous techniques: use circuit/arch. to lower leakage
This technique: use dev/ckt/arch opt. to lower leakage
Main idea: high Vt device + forward body-biasing
0.E+00
2.E-04
4.E-04
6.E-04
8.E-04
1.E-03
0 0.2 0.4 0.6 0.8 1 1.2
Gate voltage (V)
Drain
Current(A/um) Super high Vt + FBB
Super high Vt
+ ZBB
Nominal Vt + ZBB
17%3%
Nominal Vt=270mV
Super high Vt=350
Kaushik Roy, ECE, Purdue University
x32 Forward Body-Biased Subarray
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y y
...
..
...
...
..
0.4V powersupply
SUBSL
32
32
WL0
WL31
VPW
ELL
M3
M2
M1
... MN
MA MP
Kaushik Roy, ECE, Purdue University
Body Transition Delay Hiding
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Subarray turned on ahead of time using SUBSL
Extra time for body-bias transition to complete
SUBSL
VPNWE
LL
WL
Standby activestandby
A[N-1:0]
Kaushik Roy, ECE, Purdue University
Body Transition Energy Reduction
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32KB L1 inst. cache, SimpleScalar, 500M cycles
93% of the accesses hit the same subarray in the next access:locality of reference
Transition energy wasted only in 7% of accesses
SPEC2000
Kaushik Roy, ECE, Purdue University
95% 92%91%
96%
90%
94% 95% 93%
0%
20%
40%
60%
80%
100%
vpr
gcc
gzip
mcf
perlb
mk
vortex
bzip
2
averag
ePerc
entageofconsecutiv
e
acce
ssestosa
mesubarray
tline Performance Under Iso-Leakage0 12
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SBSRAM delay penalty: 3 transistor stack
FBSRAM delay penalty: + diffusion capacitance
FBSRAM is 7.3% faster than SBSRAM under iso-leakage
0.00
0.02
0.04
0.06
0.08
0.10
0.12
0 40 80 120 160 200Time (ps)
Diffe
rentialvo
ltage(V)
ConventionalFBSRAMSBSRAM
SenseAmp
activates
t=138ps
t=164ps
VBL
VBLB
Vdiff
t=152ps
Kaushik Roy, ECE, Purdue University
ummary
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y
Leakage is critically dependent on process and environmental variations
Leakage control through two promising techniques Power supply control
Threshold voltage control
Leakage will be the key design variable in next generation ICs