ee210 digital electronics class lecture 10 june 19, 2008

EE210 Digital Electronics

Class Lecture 10

June 19, 2008

Home Work No. 5 (Due June 26, 2008 )

Problems at the End Of Chapter 10.

1. Problem D10.25

2. Problem D10.26

3. Problem D10.46

4. Problem D10.47

In This ClassIn This Class

We Will Continue to Discuss:

Complete CMOS Gates

10.3.9 Effects of Fan-in and Fan-out on Propagation Delay

10.4 Pseudo-NMOS Logic Ckts

10.5 Pass-Transistor Logic Ckts

10.3.9 Effects of Fan-in and Fan-out10.3.9 Effects of Fan-in and Fan-out• As compared to other MOS logic, CMOS logic

requires two transistors (NMOS and PMOS) for each additional Input

• This results in Increase in Chip Area and Total Effective Capacitance per gate hence Increase in Propagation Delay

• Increase in number of in-put (fan-in) increases size and increase tp and due to that there is limit on fan-in of the NAND gate to 4.

• For higher inputs clever logic design is required

10.3.9 Effects of Fan-in and Fan-out10.3.9 Effects of Fan-in and Fan-out

• Increase in gate’s fan-out adds directly to its load capacitance and increases propagation delay

• Thus apart from many advantages, CMOS suffers from increased circuit complexity when fan-in and fan-out are increased

• In next two sections we shall study some simplified forms of CMOS logic that reduces this complexity, however, we will loose some advantages of CMOS

10.4 Pseudo-NMOS Logic Ckts10.4 Pseudo-NMOS Logic Ckts

10.4.1 Pseudo-NMOS Inverter10.4.1 Pseudo-NMOS Inverter

Input is applied at QN gate and QP gate is grounded, thus QP acts as an active load for QN.

Note that before even going into more details the advantage over CMOS is already obvious: One transistor (NMOS) for each input

10.4.2 Static Characteristics10.4.2 Static Characteristics

• The static characteristics of pseudo-NMOS inverter can be derived in similar manner as we did for CMOS inverter

• So the drain currents of QN and QP are:

where Vtn = -Vtp = Vt and kn=kn’(W/L)n and kp=kp

’(W/L)p

• To Obtain VTC, we superimpose load curve (QP iD-vDS) on the QN iD-vDS characteristics for various values of vGS=vI

10.32) (Eq.triode)(for])(2

1))([(

10.31) (Eq.)saturation(for,)(2

1

10.30) (Eq.triode)(for]2

1)[(

10.29) (Eq.)saturation(for,)(2

1

2

2

2

2

tOODDODDtDDpDP

tOtDDpDP

tIOOOtInDN

tIOtInDN

VvvVvVVVki

VvVVki

VvvvvVvki

VvvVvki

10.4.2 Static Characteristics10.4.2 Static CharacteristicsNOTE that:

1. QP has much lower saturation current than QN at vI=VDD. This is because pseudo-NMOS inverter usually designed so that kn is 4 to 10 times kp.

In fact, r ≡ kn/kp determines all the breakpoints of VTC and noise margins. High value of r reduces VOL and widens NMs.

2. One tends to think of Qp as constant-current source, but it actually operates in saturation for only a small range of vO ≤ Vt. Rest is in triode region

10.4.2 Static Characteristics10.4.2 Static CharacteristicsNow consider two extreme cases of vI: When vI=0, QN is cut off and QP is operating in the triode region with zero current and zero drain-source voltage. Point A, where vO=VOH=VDD, Static current is zero.

When vI=VDD the operating point is E. Unlike CMOS here VOL is not zero – a disadvantage.Another disadvantage is that the gate conducts Istat in low output state, thus there will be static power dissipation: PD=IstatxVDD

10.4.3 Derivation of VTC10.4.3 Derivation of VTC

• VTC of pseudo-NMOS inverter has four regions labeled I thru IV corresponding to different modes of operation of QN and QP.

Region Segment QN QP Condition

I AB Cutoff Triode vI < Vt

II BC Saturation Triode vO ≥ vI-Vt

III CD Triode Triode Vt ≤ vO ≤ vI-Vt

IV DE Triode Saturation vO ≤ Vt


Region I (Segment AB)

vO = VOH = VDD

Region II (Segment BC)

Equating iDN and iDP and using kn=rkp and some manipulation

1

)1(

)()( 22

r

VVVV

rr

VVVV

VvrVVVv

tDDtM

tDDtIL

tItDDtO






10.4.3 Derivation of VTC10.4.3 Derivation of VTCRegion III (Segment CD)

Being short segment is not very important. Point D is vO = Vt

.







Region IV (Segment DE)

Equating iDN and iDP and using kn=rkp results

rVVV

VVr

VV

VVr

VvVvv

tDDOL

tDDtIH

tDDtItIO

111)(

)(3

2

)(1

)()( 22







Finally, we use these equations to determine NML and NMH

Since VDD and Vt are determined by the process technology the only parameter for controlling the values of VOL and the noise margins is the ratio r.

rVVNM

rrrVVVNM

tDDH

tDDtL

3

21)(

)1(

1111)(

10.4.4 Dynamic Operation10.4.4 Dynamic Operation

• Similar procedure as CMOS inverter is used to find tPLH and tPHL for the pseudo-NMOS inverter and are given as:

• Although these are identical to CMOS inverter, the pseudo-NMOS inverter has a special problem: Since kp is r times smaller than kn, tPLH will be r times larger than tPHL. Thus ckt exhibits asymmetrical performance.

rVk

Ct

Vk

Ct

DDnPHL

DDpPLH

of valuelargefor 7.1

7.1

10.4.6 Gate Circuits10.4.6 Gate Circuits

Except for the load device, pseudo-NMOS gate circuit is identical to PDN of CMOS gate

Note that NOR and NAND gates each require five transistors compared to eight in CMOS

10.4.7 Concluding Remark10.4.7 Concluding Remark

• The pseudo-NMOS is particularly suited for applications in which the output remains high most of the time. Since gate dissipates static power only in low-output state, the static power dissipation in this application is low.

• The propagation delay can be made as short as necessary for the output transition from high-to-low.

• This type of application can be found in ROMs.

Example 10.3Example 10.3

10.5 Pass-Transistor Logic Ckts10.5 Pass-Transistor Logic Ckts• A simple approach to implement logic functions is to use

series and parallel combination of switches controlled by input logic variables to connect input and output nodes

These switches can be NMOS transistor

or pair of complementary MOS transistor

connected as CMOS transmission

gate configuration

10.5 Pass-Transistor Logic Ckts10.5 Pass-Transistor Logic Ckts• This provides simple form of logic circuit that is

particularly suited for special logic functions and is frequently used in conjunction with CMOS logic to implement such functions efficiently

• Because this form of logic utilizes MOS transistors in series path from input to output, to PASS or block signal, it is known as Pass-Transistor Logic (PTL)

• As CMOS transmission gates are frequently used to implement switches in these logic circuits an alternative name as Transmission-gate logic. Generally both these names are used irrespective of actual switches

• Although simple, PTL logic circuits design require care

10.5.1 Essential Design Requirement10.5.1 Essential Design Requirement• Essential requirement to design PTL circuit is to ensure that every ckt

node has at all times a low-resistance path to VDD or ground.

Switch S1 is used to form AND Function

of its controlling variable B and

variable A at the CMOS inverter output.

Y of PTL is connected to input of another

inverter. When B is Hi S1 closes and Y=A.

Node Y will be connected to either VDD

(if A is Hi) or to ground (if A is Low). But what

happens when B is low and S1 opens? Node Y will now

become high-impedance node. If vY was zero it will remain so. However,

if it was VDD, it will be maintained by the charge on parasitic C, for only

a time. Leakage current will slowly discharge C and vY will be lost.

10.5.1 Essential Design Requirement10.5.1 Essential Design Requirement

Problem can be easily solved by establishing a low-resistance path for node Y that is activated when B goes low (S1 opens).

In the improved design

here another switch S2

is controlled by B (bar)

And connects Y and ground.

10.5.2 Operation with NMOS as SW10.5.2 Operation with NMOS as SW

Using NMOS as switch in PTL results in small area and small node capacitances. These advantages are achieved at the expense of serious shortcomings in both static characteristics and the dynamic performance of the circuit.


When vI goes to Zero


Technique to correct ‘Poor 1’

10.5.3 Use of CMOS Transmission 10.5.3 Use of CMOS Transmission Gate as SWGate as SW

10.5.4 Pass-Transistor Logic Circuit 10.5.4 Pass-Transistor Logic Circuit ExamplesExamples

ee210 digital electronics class lecture 10 june 19, 2008

Documents