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1 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Electrical Systems
Peter AvitabileMechanical Engineering DepartmentUniversity of Massachusetts Lowell
2 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Electrical Systems
Passive Electrical ElementsResistor, Inductor, Capacitor
Elemental Relations for Voltages
ResistorR
RVRi+ −
RR RiV =Voltage Resistance Current
)ampere/voltohm( =
Resistors dissipate heat – no energy storage
3 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Elemental Relations for Voltages cont.
Inductor
Capacitor
Inductors generate considerable resistance
dtdiLV L
L =
Voltage Inductance current of change of Rate
sec)/( amponeofchangeofrateHenry =)( voltoneofemfaninducewill
L
LV+ −
dtic1V cC ∫=
VoltageeCapacitanc
Current
)sec(volt
ampFarad =Note C=q/vc q-charge
Note also i=dq/dt and vc=q/c
cV+ −
ci
Li
4 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Elemental Relations for Currents
ResistorR
Vi RR =
Inductor
Capacitor
dtVL1i LL ∫=
dtdVci c
C =
5 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Electrical Systems
Rei =
321 eeee ++=
Ohm’s Law states that the current in a circuit is proportional to the total electromotive (emf) force acting in the circuit and inversely proportional to the total resistance in the circuit.
Series
i – current (amps); e – emf (volt); R – resistanace (Ohm)1R 2R 3R
B
1e 2e 3eAi
effective321 RRRRie
=++=
Ve ≈
6 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Electrical Resistance
Parallel
33
22
11 R
ei;Rei;
Rei ===
Since
Then
1R2R 3R
1i 2i 3i
e
321 iiii ++=
effective321 Re
Re
Re
Rei =++=
321eff R1
R1
R1
R1
++=133221
321eff RRRRRR
RRRR++
=∴
7 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Kirchoff’s Law
Two Law’s exist: Current Law (node law)Voltage Law (loop law)
Current Law (node law)The algebraic sum of all currents entering and leaving a node is zero.
0iii 321 =++ 0)iii( 321 =++− 0iii 321 =−+
3i
2i
1i 3i
2i
1i 3i
2i
1i
8 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Kirchoff’s Law
Consider the circuit
The instant the switch is closed, the current i(o)=zero because the inductor cannot change from zero to a finite value instantaneously
RL VVV +=
VRidtdiL =+
i LR
+−RV
LV+
−V+
−
9 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Kirchoff’s Law
Take the Laplace Transform
[ ]SE)s(RI)0(i)s(sIL =+−
+−=
+=
)LR(S
1S1
RE
)RLS(SE)s(I
SE)s(I)RLS( =+
Since i(0)=0
OR
Note that E and V are often used for voltage
10 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Kirchoff’s Law
The inverse laplace gives
−=
− t)LR(
e1RE)t(i
RLat
RE
=τ
Prove that the slope of the function intersects the final value
RE
RE63.0
RL
11 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Voltage Law (Loop Law)
The algebraic sum of the voltages around the loop in an electrical circuit is zero.
0VVVV CRL =−++
L
LV+ −
V
+
−
C
R+− CV RV
+
−
12 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Voltage Law (Loop Law) cont.
Continuing with this loop, the diff. eq. isdti
C1V;RiV;
dtdiLV CCRR
LL ∫===
Then
Taking a derivative to eliminate the integral∫ =++ aVdti
ot
c1Ri
dtdiL
dtdVi
C1
dtdiR
dtidL a2
2=++
Thus
ORdt
dVL1i
LC1
dtdi
LR
dtid a2
2=++
LCR
21
2LR;
LC1 2
nn =
ω=ς=ω
13 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Voltage Law (Loop Law) cont.
Taking the Laplace Transform (with IC=0)
)S(VLS)S(I)
LC1S
LRS( a
2 =++
The Transfer Function is
Rearranging
++
=)
LC1(S)
LR(SL
S)S(V)S(I
2
Recalling the relation
)S(VCS)S(I)1RCSLCS( a2 =++
∫= dtic1V cc
14 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Voltage Law (Loop Law) cont.
The Transfer Function relating the input voltage to the voltage drop across the capacitor is
Recalling the relation ∫= dtic1V cc
++
==
)LC(1S)
LR(SLC
1)S(V
)S(ICS1
)S(V)S(V
2aa
c
15 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Operational Amplifier
An OP-AMP is an electronic amplifier with a single output and very high voltage gain (105 to 106) –low current!
The OP-AMP amplifies the difference in voltages and and is often referred to as a differential amplifier
In this configuration, an OP-AMP is inherently unstable –to stabilize it a negative feedback is often used.
+e( )
GeneralIn eeKeo −+ −=
−
+
−e
+e −e
16 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Operational AmplifierAn OP-AMP is the most widely used analog electronic device
VoltagesInput e,e BA ⇒
Bi+
Ground Signal
oioe
oz
osV
AiBe+
−+
Dz
+
Ae
GroundChassisDefinitions:
Currents Bias i,i BA ⇒ImpedanceInput alDifferenti ZD ⇒
Gain LoopOpen A ⇒
ImpedanceOutput Zo ⇒VoltageOffset Vos ⇒
Supply VoltageVs ⇒±
oe
osV
( )mVee BA −
( )AVeee osBAo −−=
17 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Operational Amplifier
Voltage Follower( )AVeee osBAo −−=
∞→A 0Vos →Assume and
oio eee
−=∞ io ee =∴
Output follows input
ieSource supplying works into an “infinite”impedance thus no current is drawn
oe does not draw current or consume power
Sometimes called a buffer amplifier
18 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Operational Amplifier
Consider an inverting amplifier shown
Since only negligible current flows into the amplifier, i1 must equal i2
1
2RR is Gain ⇒i
1
2o e
RRe −=
( )1
i1 R
'eei −=
'e
+−
ie +−
+
−
1R
1i
2R
2i
oe
( )2
o2 R
e'ei −=
Since then . Thus the approximate model is:1K >> 0'e ≈
21 Re
Re oi −=
19 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Operational Amplifier
Consider a non-inverting amplifier shown'e
+−
ie+
−
+
−
1R 2R
oe
Since
i1
2o e1
RRe
+=
1
2RR is Gain ⇒
1K >>
And ifK1
RRR
21
1 >>+
Then an approximate model is
021
1i
021
1i0
e)K1
RRR(e
or
)eRR
Re(Ke
++
=
+−=
For this circuit
20 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Low-Pass Filter
Transfer Function
( ) ( )sXXs
ee
i
o
i
o =
ω= js
oe
RC≈τ
ie
Electrical
Frequency response function is evaluated atMechanical
iX
K B
oX
KB
≈τ
1j1+τω
=
1s1+τ
=
R C
21 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Low-Pass Filter
Passive styled filters have various advantages:
Very low noise output
No power required
Versatile
Wide dynamic range
22 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
High-Pass Filter
Transfer Function
( ) ( )sXXs
ee
i
o
i
o =
1ss+ττ
=
oe
RC≈τ
ie
Electrical
RC
ω= jsFrequency response function is evaluated at
1sj+ττω
=Mechanical
iX
KB
oX
KB
≈τ
23 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Cascade a low pass and high pass filter together
Band-Pass Filter
1s1
1 +τ 1ss
2
2+τ
τ
12 τ>τ
24 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Integration (Approximation Using Low Pass)
+−
ie +−
+
−
R
C
oe
( )1j
1jee
i
o+ωτ
=ω
Now if then1>>ωτ
( )ωτ
=ωj1j
ee
i
o
Or( )
s1s
ee
i
oτ
= dte1e io ∫τ≈∴
25 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Differentiation (Approximation Using High Pass)
+−
ie +−
+
−
RC
oe
( )1j
jjee
i
o+ωτ
ωτ=ω
Now if then1<<ωτ
( ) ωτ=ω jjee
i
o
Or
dtdee i
o τ=∴( ) ssee
i
o τ≈
These circuits are sensitive to noise upon differentiating
BEWARE!!
26 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Differentiation (w/Low Pass Filter)
( )1CsR
CsRsee
1
2
i
o+
−=
Accurate for 1CR1 <<ω
1
2RR
But amplifies high frequency noise by
+−
ie +−
+
−
2RC
oe
1R
27 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Differentiation (w/Low Pass Filter & Noise Atten.)
( )( )( )1sCR1sCR
sCRsee
1122
12
i
o++
−=
+−
ie +−
+
−
2R
1C
oe
1R2C
28 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
ElectroMechanical SystemsArmature-controlled DC motors are popular. Field Controlled DC motors are not as popular.
Elemental RelationsElectrical and mechanical parts are coupled. The mechanical motion of the rotor relative to the stator creates an electromotive force voltage (EMF effect). The back EMF voltage across the DC motor is proportional to angular speed of the rotor.
while the torque developed by the motor is proportional to the current
θ=ω= &eeb KKe
iKT T=
29 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
ElectroMechanical Systems
where
iKT T=
oltageback emf veb −ntdisplacemeangular−θ
velocityangular−ω=θ&motor)by (exertedrotor toapplied torqueT −
)(motor ofconstant emf KRPMKV
e −
)(motor ofconstant torque K Ampoz
tf−
Conversion:
RPM
fK
V741.0Aoz-in1 =
30 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Armature-Controlled DC Motors
shaftof dampingc −disk of dampingcd −
current armatureia − (constant)current field if −
disk of inertia mass Jd −
rotor of inertia mass JR −
dcbe
RJ
aR aL
+
−−
+ai
dJ
θ=ωθ &,
c,k )t(TL
shaft stifftorsionalk −inductance armature La −resistance armature R a −
voltagearmature a −ν
aν
31 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Armature-Controlled DC MotorsRigid Shaft – Lump the rotor, shaft and disk together so that
dr JJJ +=
aν
0e0V abLRdrop aa=ν−+ν+ν=∑
One input,
Two outputs, θ and ia
For the electrical circuit, the loop method gives
Then, ( )θ=ω=ν=++ &eebab
aaaa KKee
dtdiLiR
So thataeaa
aa KiR
dtdiL ν=θ++ &
32 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Armature-Controlled DC MotorsFor the mechanical part
θ=θ−+ &&& JBTT dL
Then
Latd TiKBJ =−θ+θ &&&
J
θ
θ&dBLTT +
(Note: Voltage is input to system but current is input to mechanical part)
System Equations
Latd TiKBJ =−θ+θ &&&
aeaaa
a KiRdt
diL ν=θ++ &
OR
ν
=
θ
−+
θ
+
θ
a
L
aa
ta
ae
d
2a
2 TiR0
K0
dtdi
LK0B
dtid
000J &&&
33 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Armature-Controlled DC MotorsExpressing the equations using (since )θ=ωω &
Latd TiKBJ =−ω+ω&
aeaaa
a KiRdtdiL ν=ω++
ν
=
ω
−+
ω
a
L
aae
tda
a
TiRK
KB
dtdi
L00J &
34 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Armature-Controlled DC Motors – Laplace TransformThe Laplace Transform gives
( ) 0KKRBsJRLBsJL teadaad2
a =++++
=
Ω
+
−+)s(V)s(T
)s(I)s(
RsLKKBJs
a
L
aaae
td
After some manipulation, the characteristic equation is given by
( )a
tead2n JL
KKRB +=ω
After putting this in standard form,
( )a
aadn JL
JRLB2 +=ζω
35 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Armature-Controlled DC Motors – Laplace TransformThe transfer functions of interest are
( ) teadaad2
a
t
a KKRBsJRLBsJLK
)s(V)s(
++++=
Ω
++
++
=θ
a
tead
a
aad2
a
t
a
JLKKRBs
JLJRLBss
JLK
)s(V)s(
Note: A more complex model which includes a flexible shaft can also be developed.
36 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Example - Circuit AttenuationA low frequency signal (at 3 Hz) is to be measured but is contaminated by a higher frequency component such as 60 Hz noise for instance.
Filter
R C
in sig
outV
scope
outVinV
The filter must be selected to attenuate the 60 Hz noise without significantly affecting the actual signal attenuation by no more than a factor of 0.9.
A first order low pass filter (RC circuit)
37 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Example – Circuit AttenuationFilter Transfer Function
1RCs1
)s(V)s(V)s(H
in
out+
==
( )9.0
1
1VV
)j(H2in
out =+ωτ
==ω
Since
The magnitude of the frequency response function is
s 0.026 constant timeRCτ ==
( )( ) 13Hz2
10.92 +π⋅τ
=
At 60 Hz, the amplitude is ( )[ ] 093.016020257.0 21
2 =+π⋅⋅⋅−
with RC - possible values s026.0= F2.0C µ=Ω= k130R
38 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Force Voltage Analogy
CurrentCurrentiVelocityVelocity
ChargeChargeqxDisplacementDisplacement
Reciprocal of CapacitanceReciprocal of Capacitance1/CkSpring ConstantSpring Constant
ResistanceResistanceRcViscous FrictionViscous Friction
InductanceInductanceLmMassMass
VoltageVoltagevfForceForce
ElectricalElectricalMechanicalMechanical
x&
)t(fkxxcxm =++ &&& ν=++ qC1qRqL &&&
39 Dr. Peter AvitabileModal Analysis & Controls Laboratory22.451 Dynamic Systems – Electrical
Force Current Analogy
VoltageVoltageVelocityVelocity
Magnetic FluxMagnetic FluxxDisplacementDisplacement
Reciprocal of InductanceReciprocal of Inductance1/LkSpring ConstantSpring Constant
Reciprocal of ResistanceReciprocal of Resistance1/RcViscous FrictionViscous Friction
CapacitanceCapacitanceCmMassMass
CurrentCurrentifForceForce
ElectricalElectricalMechanicalMechanical
)t(fkxxcxm =++ &&& iL1
R1C =ψ+ψ+ψ &&&
x& ν
ψ