top252-262 topswitch-hx family - power integrations · top252-262 topswitch-hx family june 2013...

TOP252-262 TOPSwitch-HX Family

www.powerint.com June 2013

Enhanced EcoSmart™, Integrated Off-Line Switcher with Advanced Feature Set and Extended Power Range

™

Product Highlights

Lower System Cost, Higher Design Flexibility • Multi-mode operation maximizes efficiency at all loads• New eSIP-7F and eSIP-7C packages

• Low thermal impedance junction-to-case (2 °C per watt)• Low height is ideal for adapters where space is limited• Simple mounting using a clip to aid low cost manufacturing• Horizontal eSIP-7F package ideal for ultra low height adapter

and monitor applications• Extended package creepage distance from DRAIN pin to

adjacent pin and to heat sink• No heat sink required up to 35 W using P, G and M packages

with universal input voltage and up to 48 W at 230 VAC• Output overvoltage protection (OVP) is user programmable for

latching/non-latching shutdown with fast AC reset• Allows both primary and secondary sensing

• Line undervoltage (UV) detection prevents turn-off glitches• Line overvoltage (OV) shutdown extends line surge limit• Accurate programmable current limit• Optimized line feed-forward for line ripple rejection• 132 kHz frequency (254Y-258Y and all E/L packages) reduces

transformer and power supply size • Half frequency option for video applications

• Frequency jittering reduces EMI filter cost

Figure 1. Typical Flyback Application.

• Heat sink is connected to SOURCE for low EMI• Improved auto-restart delivers <3% of maximum power in

short circuit and open loop fault conditions• Accurate hysteretic thermal shutdown function automatically

recovers without requiring a reset• Fully integrated soft-start for minimum start-up stress• Extended creepage between DRAIN and all other pins

improves field reliability

PI-4510-100206

AC IN

DC OUT

D

S

C TOPSwitch-HXCONTROL

V

+

-

F X

Output Power Table

Product5230 VAC ±15%4 85-265 VAC

Adapter1 Open Frame2 Peak3 Adapter1 Open

Frame2 Peak3

TOP252PN/GN9 W 15 W

21 W6 W 10 W

13 W

TOP252MN 21 W 13 W

TOP253PN/GN15 W 25 W

38 W9 W 15 W

25 W

TOP253MN 43 W 29 W


47 W11 W 20 W

30 W

TOP254MN 62 W 40 W


54 W13 W 22 W

35 W

TOP255MN 81 W 52 W


63 W15 W 26 W

40 W

TOP256MN 98 W 64 W


70 W19 W 30 W

45 W

TOP257MN 119 W 78 W


77 W22 W 35 W

50 W

TOP258MN 140 W 92 W

Table 1. Output Power Table. (for notes see page 2).

Product5230 VAC ±15% 85-265 VAC

Adapter1 Open Frame2 Adapter1 Open

Frame2

TOP252EN/EG 10 W 21 W 6 W 13 WTOP253EN/EG 21 W 43 W 13 W 29 WTOP254EN/YN/EG 30 W 62 W 20 W 43 WTOP255EN/YN/EG 40 W 81 W 26 W 57 WTOP255LN 40 W 81 W 26 W 57 W

TOP256EN/YN/EG 60 W 119 W 40 W 86 WTOP256LN 60 W 88 W 40 W 64 WTOP257EN/YN/EG 85 W 157 W 55 W 119 WTOP257LN 85 W 105 W 55 W 78 WTOP258EN/YN/EG 105 W 195 W 70 W 148 WTOP258LN 105 W 122 W 70 W 92 W

TOP259EN/YN/EG 128 W 238 W 80 W 171 WTOP259LN 128 W 162 W 80 W 120 WTOP260EN/YN/EG 147 W 275 W 93 W 200 WTOP260LN 147 W 190 W 93 W 140 WTOP261EN/YN/EG 177 W 333 W 118 W 254 WTOP261LN 177 W 244 W 118 W 177 WTOP262EN6 177 W 333 W 118 W 254 WTOP262LN6 177 W 244 W 118 W 177 W

Rev. H 06/13

2

TOP252-262

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EcoSmart™– Energy Efficient• Energy efficient over entire load range• No-load consumption

• Less than 200 mW at 230 VAC• Standby power for 1 W input

• >600 mW output at 110 VAC input• >500 mW output at 265 VAC input

Description

TOPSwitch-HX cost effectively incorporates a 700 V power MOSFET, high voltage switched current source, PWM control, oscillator, thermal shutdown circuit, fault protection and other control circuitry onto a monolithic device.

PI-4973-122607

ACIN

DCOUT

D

S

CTOPSwitch-HXCONTROL

V

+

-

GX

Figure 2. Typical Flyback Application TOP259YN, TOP260YN and TOP261YN.

Y Package Option for TOP259-261In order to improve noise-immunity on large TOPSwitch-HX Y package parts, the F pin has been removed (TOP259-261YN are fixed at 66 kHz switching frequency) and replaced with a SIGNAL GROUND (G) pin. This pin acts as a low noise path for the C pin capacitor and the X pin resistor. It is only required for the TOP259-261YN package parts.

Notes for Table 1: 1. Minimum continuous power in a typical non-ventilated

enclosed adapter measured at +50 °C ambient. Use of an external heat sink will increase power capability.

2. Minimum continuous power in an open frame design at +50 °C ambient.

3. Peak power capability in any design at +50 °C ambient.4. 230 VAC or 110/115 VAC with doubler.5. Packages: P: DIP-8C, G: SMD-8C, M: SDIP-10C,

Y: TO-220-7C, E: eSIP-7C, L: eSIP-7F. See part ordering information.

6. TOP261 and TOP262 have the same current limit set point. In some applications TOP262 may run cooler than TOP261 due to a lower RDS(ON) for the larger device.

Rev. H 06/13

3

TOP252-262

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Section List

Functional Block Diagram ....................................................................................................................................... 4

Pin Functional Description ...................................................................................................................................... 6

TOPSwitch-HX Family Functional Description ....................................................................................................... 7 CONTROL (C) Pin Operation .................................................................................................................................... 8 Oscillator and Switching Frequency .......................................................................................................................... 8 Pulse Width Modulator ............................................................................................................................................ 9 Maximum Load Cycle .............................................................................................................................................. 9 Error Amplifier .......................................................................................................................................................... 9 On-Chip Current Limit with External Programmability ............................................................................................... 9 Line Undervoltage Detection (UV) ........................................................................................................................... 10 Line Overvoltage Shutdown (OV) ............................................................................................................................ 11 Hysteretic or Latching Output Overvoltage Protection (OVP)................................................................................... 11 Line Feed-Forward with DCMAX Reduction .............................................................................................................. 13 Remote ON/OFF and Synchronization .................................................................................................................... 13 Soft-Start ............................................................................................................................................................... 13 Shutdown/Auto-Restart ......................................................................................................................................... 13 Hysteretic Over-Temperature Protection ................................................................................................................. 13 Bandgap Reference ............................................................................................................................................... 13 High-Voltage Bias Current Source .......................................................................................................................... 13

Typical Uses of FREQUENCY (F) Pin ...................................................................................................................... 15

Typical Uses of VOLTAGE MONITOR (V) and EXTERNAL CURRENT LIMIT (X) Pins .......................................... 16

Typical Uses of MULTI-FUNCTION (M) Pin ........................................................................................................... 18

Application Examples .............................................................................................................................................. 21 A High Efficiency, 35 W, Dual Output – Universal Input Power Supply ..................................................................... 21 A High Efficiency, 150 W, 250-380 VDC Input Power Supply .................................................................................. 22 A High Efficiency, 20 W Continuous – 80 W Peak, Universal Input Power Supply ................................................... 23 A High Efficiency, 65 W, Universal Input Power Supply ........................................................................................... 24

Key Application Considerations .............................................................................................................................. 25 TOPSwitch-HX vs.TOPSwitch-GX ....................................................................................................................... . 25 TOPSwitch-HX Design Considerations .................................................................................................................. 26 TOPSwitch-HX Layout Considerations ................................................................................................................... 27 Quick Design Checklist .......................................................................................................................................... 31 Design Tools .......................................................................................................................................................... 31

Product Specifications and Test Conditions .......................................................................................................... 32

Typical Performance Characteristics .................................................................................................................... 39

Package Outlines .................................................................................................................................................... 43

Part Ordering Information ........................................................................................................................................ 47

Rev. H 06/13

4

TOP252-262

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Figure 3a. Functional Block Diagram (P and G Packages).

Figure 3b. Functional Block Diagram (M Package).

PI-4643-082907

SHUTDOWN/ AUTO-RESTART

CLOCK

CONTROLLED TURN-ON

GATE DRIVER

CURRENT LIMIT COMPARATOR

INTERNAL UV COMPARATOR

INTERNAL SUPPLY

5.8 V 4.8 V

SOURCE (S)

SOURCE (S)

S

R

Q

DMAX

STOP SOFT START

CONTROL (C)

VOLTAGE MONITOR (V)

-

+ 5.8 V

IFB

1 V

ZC

VC

+

-

+

-

+

-

LEADING EDGE

BLANKING

√ 16

1

HYSTERETIC THERMAL

SHUTDOWN

SHUNT REGULATOR/ ERROR AMPLIFIER +

-

DRAIN (D)

ON/OFF

DCMAX

DCMAX

0

OV/ UV

OVP V

VI (LIMIT) CURRENT LIMIT

ADJUST

VBG + VT

LINE SENSE

SOFT START

OFF

F REDUCTION

F REDUCTION

STOP LOGIC

EXTERNAL CURRENT LIMIT (X)

OSCILLATOR WITH JITTER

PWM

KPS(UPPER)

KPS(LOWER)

SOFT START IFB IPS(UPPER) IPS(LOWER)

KPS(UPPER)KPS(LOWER)

PI-4508-120307


CLOCK

CONTROLLED TURN-ON

GATE DRIVER



INTERNAL SUPPLY

5.8 V 4.8 V

KPS(UPPER)

KPS(LOWER)

SOURCE (S)

SOURCE (S)

S

R

Q

DMAX

STOP SOFT START

CONTROL (C)

MULTI- FUNCTION (M)

-

+ 5.8 V

IFB

ZC

VC

+

-

+

-

+

-

LEADING EDGE

BLANKING

√ 16

1

HYSTERETIC THERMAL

SHUTDOWN


-

DRAIN (D)

ON/OFF

DCMAX

DCMAX

0

OV/ UV

OVP V


ADJUST

VBG + VT

LINE SENSE

SOFT START



OFF

F REDUCTION

F REDUCTION

STOP LOGIC


PWM

Rev. H 06/13

5

TOP252-262

www.powerint.com

Figure 3c. Functional Block Diagram (TOP254-258 YN Package and all eSIP Packages).

PI-4511-082907


CLOCK

CONTROLLED TURN-ON

GATE DRIVER



INTERNAL SUPPLY

5.8 V 4.8 V

SOURCE (S)

SOURCE (S)

S

R

Q

DMAX

STOP SOFT START

CONTROL (C)

VOLTAGE MONITOR (V)

FREQUENCY (F)

-

+ 5.8 V

IFB

1 V

ZC

VC

+

-

+

-

+

-

LEADING EDGE

BLANKING

√ 16

1

HYSTERETIC THERMAL

SHUTDOWN


-

DRAIN (D)

ON/OFF

DCMAX

DCMAX 66k/132k

0

OV/ UV

OVP V


ADJUST

VBG + VT

LINE SENSE

SOFT START

OFF

F REDUCTION

F REDUCTION

STOP LOGIC



PWM

KPS(UPPER)

KPS(LOWER)



PI-4974-122607


CLOCK

CONTROLLED TURN-ON

GATE DRIVER



INTERNAL SUPPLY

5.8 V 4.8 V

SIGNALGROUND (G)

SOURCE (S)

S

R

Q

DMAX

STOP SOFT START

CONTROL (C)

VOLTAGE MONITOR (V)

-

+ 5.8 V

IFB

1 V

ZC

VC

+

-

+

-

+

-

LEADING EDGE

BLANKING

√ 16

1

HYSTERETIC THERMAL

SHUTDOWN


-

DRAIN (D)

SOURCE (S)

ON/OFF

DCMAX

DCMAX

0

OV/ UV

OVP V


ADJUST

VBG + VT

LINE SENSE

SOFT START

OFF

F REDUCTION

F REDUCTION

STOP LOGIC



PWM

KPS(UPPER)

KPS(LOWER)



Figure 3d. Functional Block Diagram TOP259YN, TOP260YN, TOP261YN.

Rev. H 06/13

6

TOP252-262

www.powerint.com

Pin Functional Description

DRAIN (D) Pin:High-voltage power MOSFET DRAIN pin. The internal start-up bias current is drawn from this pin through a switched high-voltage current source. Internal current limit sense point for drain current.

CONTROL (C) Pin:Error amplifier and feedback current input pin for duty cycle control. Internal shunt regulator connection to provide internal bias current during normal operation. It is also used as the connection point for the supply bypass and auto-restart/ compensation capacitor.

EXTERNAL CURRENT LIMIT (X) Pin (Y, M, E and L package):Input pin for external current limit adjustment and remote ON/OFF. A connection to SOURCE pin disables all functions on this pin.

Figure 4. Pin Configuration (Top View).

X

PI-

4711

-021

308

DCInput

Voltage

+

-

D

S

CCONTROL

V

RIL

RLS

12 kΩ

4 MΩ

VUV = IUV × RLS + VV (IV = IUV)VOV = IOV × RLS + VV (IV = IOV) For RLS = 4 MΩ

DCMAX@100 VDC = 76%DCMAX@375 VDC = 41%

For RIL = 12 kΩ ILIMIT = 61% See Figure 55b for other resistor values (RIL) to select different ILIMIT values.

VUV = 102.8 VDC VOV = 451 VDC

Figure 5. TOP254-258 Y and All M/E/L Package Line Sense and Externally Set Current Limit.

PI-4712-120307

DCInput

Voltage

+

-

D M

S

C

VUV = IUV × RLS + VM (IM = IUV)VOV = IOV × RLS + VM (IM = IOV) For RLS = 4 MΩ VUV = 102.8 VDC VOV = 451 VDC


CONTROL

RLS 4 MΩ

Figure 7. P/G Package Line Sense.

X G

PI-

4983

-021

308

DCInput

Voltage

+

-

D

S

CCONTROL

V

RIL

RLS

12 kΩ

4 MΩ

VUV = IUV × RLS + VV (IV = IUV)VOV = IOV × RLS + VV (IV = IOV) For RLS = 4 MΩ




Figure 6. TOP259-261 Y Package Line Sense and External Current Limit.

VOLTAGE MONITOR (V) Pin (Y & M package only):Input for OV, UV, line feed forward with DCMAX reduction, output overvoltage protection (OVP), remote ON/OFF and device reset. A connection to the SOURCE pin disables all functions on this pin.

MULTI-FUNCTION (M) Pin (P & G packages only):This pin combines the functions of the VOLTAGE MONITOR (V) and EXTERNAL CURRENT LIMIT (X) pins of the Y package into one pin. Input pin for OV, UV, line feed forward with DCMAX

PI-4644-091108

Tab InternallyConnected to SOURCE Pin

Tab InternallyConnected to SOURCE Pin

Lead Bend Outward from Drawing(Refer to eSIP-7F PackageOutline Drawing)

Exposed Pad(Hidden) InternallyConnected to SOURCE Pin

Y Package (TO-220-7C)

D

C S

S

S

S

S

S

S

S

S

7D

5F

4S

3C

2X

1V

7D

5S

4F

3C

2X

1V

7D

5S

4F

3C

2X

1V

7D

5G

4S

3C

2X

1V

M

P and G Package

M Package

8

5

7

1

4

2

6

D

X

C

V 10

6

9

1

5

8

7

2

3

Note: Y package for TOP259-261

Note: Y package for TOP254-258

E Package (eSIP-7C)

L Package (eSIP-7F)

Y Package (TO-220-7C)

Rev. H 06/13

7

TOP252-262

www.powerint.com

PI-4713-021308

DCInput

Voltage

+

-

D M

S

C

For RIL = 12 kΩ ILIMIT = 61%

CONTROLRIL

See Figure 55b for other resistor values (RIL) to select different ILIMIT values.


Figure 8. P/G Package Externally Set Current Limit.

reduction, output overvoltage protection (OVP), external current limit adjustment, remote ON/OFF and device reset. A connection to SOURCE pin disables all functions on this pin and makes TOPSwitch-HX operate in simple three terminal mode (like TOPSwitch-II).

FREQUENCY (F) Pin (TOP254-258Y, and all E and L packages):Input pin for selecting switching frequency 132 kHz if connected to SOURCE pin and 66 kHz if connected to CONTROL pin. The switching frequency is internally set for fixed 66 kHz operation in the P, G, M package and TOP259YN, TOP260YN and TOP261YN.

SIGNAL GROUND (G) Pin (TOP259YN, TOP260YN & TOP261YN only):Return for C pin capacitor and X pin resistor.

SOURCE (S) Pin:Output MOSFET source connection for high voltage power return. Primary side control circuit common and reference point.

TOPSwitch-HX Family Functional Description

Like TOPSwitch-GX, TOPSwitch-HX is an integrated switched mode power supply chip that converts a current at the control input to a duty cycle at the open drain output of a high voltage power MOSFET. During normal operation the duty cycle of the power MOSFET decreases linearly with increasing CONTROL pin current as shown in Figure 9.

In addition to the three terminal TOPSwitch features, such as the high voltage start-up, the cycle-by-cycle current limiting, loop compensation circuitry, auto-restart and thermal shutdown, the TOPSwitch-HX incorporates many additional functions that reduce system cost, increase power supply performance and design flexibility. A patented high voltage CMOS technology allows both the high-voltage power MOSFET and all the low voltage control circuitry to be cost effectively integrated onto a single monolithic chip.

Three terminals, FREQUENCY, VOLTAGE-MONITOR, and EXTERNAL CURRENT LIMIT (available in Y and E/L packages),

two terminals, VOLTAGE-MONITOR and EXTERNAL CURRENT LIMIT (available in M package) or one terminal MULTI-FUNCTION (available in P and G package) have been used to implement some of the new functions. These terminals can be connected to the SOURCE pin to operate the TOPSwitch-HX in a TOPSwitch-like three terminal mode. However, even in this three terminal mode, the TOPSwitch-HX offers many transparent features that do not require any external components:

1. A fully integrated 17 ms soft-start significantly reduces or eliminates output overshoot in most applications by sweeping both current limit and frequency from low to high to limit the peak currents and voltages during start-up.

2. A maximum duty cycle (DCMAX) of 78% allows smaller input storage capacitor, lower input voltage requirement and/or higher power capability.

3. Multi-mode operation optimizes and improves the power supply efficiency over the entire load range while maintaining good cross regulation in multi-output supplies.

Figure 9. Control Pin Characteristics (Multi-Mode Operation).

PI-4645-041107

Du

ty C

ycle

(%

) D

rain

Pea

k C

urr

ent

To C

urr

ent

Lim

it R

atio

(%

) F

req

uen

cy (

kHz)

CONTROL Current

CONTROL Current

CONTROLCurrent

ICOFFIC03IC02 IC01 IB ICD1

100

78

55

25

132

66

30

Slope = PWM Gain (constant over load range)

Auto-Restart

Variable Frequency

Mode

Low Frequency

Mode

Multi-Cycle Modulation

Jitter

Full Frequency Mode

Rev. H 06/13

8

TOP252-262

www.powerint.com

4. Switching frequency of 132 kHz reduces the transformer size with no noticeable impact on EMI.

5. Frequency jittering reduces EMI in the full frequency mode at high load condition.

6. Hysteretic over-temperature shutdown ensures automatic recovery from thermal fault. Large hysteresis prevents circuit board overheating.

7. Packages with omitted pins and lead forming provide large drain creepage distance.

8. Reduction of the auto-restart duty cycle and frequency to improve the protection of the power supply and load during open loop fault, short circuit, or loss of regulation.

9. Tighter tolerances on I2f power coefficient, current limit reduction, PWM gain and thermal shutdown threshold.

The VOLTAGE-MONITOR (V) pin is usually used for line sensing by connecting a 4 MW resistor from this pin to the rectified DC high voltage bus to implement line overvoltage (OV), under-voltage (UV) and dual-slope line feed-forward with DCMAX reduction. In this mode, the value of the resistor determines the OV/UV thresholds and the DCMAX is reduced linearly with a dual slope to improve line ripple rejection. In addition, it also provides another threshold to implement the latched and hysteretic output overvoltage protection (OVP). The pin can also be used as a remote ON/OFF using the IUV threshold.

The EXTERNAL CURRENT LIMIT (X) pin can be used to reduce the current limit externally to a value close to the operating peak current, by connecting the pin to SOURCE through a resistor. This pin can also be used as a remote ON/OFF input.

For the P and G package the VOLTAGE-MONITOR and EXTERNAL CURRENT LIMIT pin functions are combined on one MULTI-FUNCTION (M) pin. However, some of the functions become mutually exclusive.

The FREQUENCY (F) pin in the TOP254-258 Y and E/L packages set the switching frequency in the full frequency PWM mode to the default value of 132 kHz when connected to SOURCE pin. A half frequency option of 66 kHz can be chosen by connecting this pin to the CONTROL pin instead. Leaving this pin open is not recommended. In the P, G and M packages and the TOP259-261 Y packages, the frequency is set internally at 66 kHz in the full frequency PWM mode.

CONTROL (C) Pin OperationThe CONTROL pin is a low impedance node that is capable of receiving a combined supply and feedback current. During normal operation, a shunt regulator is used to separate the feedback signal from the supply current. CONTROL pin voltage VC is the supply voltage for the control circuitry including the MOSFET gate driver. An external bypass capacitor closely connected between the CONTROL and SOURCE pins is required to supply the instantaneous gate drive current. The total amount of capacitance connected to this pin also sets the auto-restart timing as well as control loop compensation.When rectified DC high voltage is applied to the DRAIN pin during start-up, the MOSFET is initially off, and the CONTROL pin capacitor is charged through a switched high voltage

current source connected internally between the DRAIN and CONTROL pins. When the CONTROL pin voltage VC reaches approximately 5.8 V, the control circuitry is activated and the soft-start begins. The soft-start circuit gradually increases the drain peak current and switching frequency from a low starting value to the maximum drain peak current at the full frequency over approximately 17 ms. If no external feedback/supply current is fed into the CONTROL pin by the end of the soft-start, the high voltage current source is turned off and the CONTROL pin will start discharging in response to the supply current drawn by the control circuitry. If the power supply is designed properly, and no fault condition such as open loop or shorted output exists, the feedback loop will close, providing external CONTROL pin current, before the CONTROL pin voltage has had a chance to discharge to the lower threshold voltage of approximately 4.8 V (internal supply undervoltage lockout threshold). When the externally fed current charges the CONTROL pin to the shunt regulator voltage of 5.8 V, current in excess of the consumption of the chip is shunted to SOURCE through an NMOS current mirror as shown in Figure 3. The output current of that NMOS current mirror controls the duty cycle of the power MOSFET to provide closed loop regulation. The shunt regulator has a finite low output impedance ZC that sets the gain of the error amplifier when used in a primary feedback configuration. The dynamic impedance ZC of the CONTROL pin together with the external CONTROL pin capacitance sets the dominant pole for the control loop.

When a fault condition such as an open loop or shorted output prevents the flow of an external current into the CONTROL pin, the capacitor on the CONTROL pin discharges towards 4.8 V. At 4.8 V, auto-restart is activated, which turns the output MOSFET off and puts the control circuitry in a low current standby mode. The high-voltage current source turns on and charges the external capacitance again. A hysteretic internal supply undervoltage comparator keeps VC within a window of typically 4.8 V to 5.8 V by turning the high-voltage current source on and off as shown in Figure 11. The auto-restart circuit has a divide-by-sixteen counter, which prevents the output MOSFET from turning on again until sixteen discharge/charge cycles have elapsed. This is accomplished by enabling the output MOSFET only when the divide-by-sixteen counter reaches the full count (S15). The counter effectively limits TOPSwitch-HX power dissipation by reducing the auto-restart duty cycle to typically 2%. Auto-restart mode continues until output voltage regulation is again achieved through closure of the feedback loop.

Oscillator and Switching FrequencyThe internal oscillator linearly charges and discharges an internal capacitance between two voltage levels to create a triangular waveform for the timing of the pulse width modulator. This oscillator sets the pulse width modulator/current limit latch at the beginning of each cycle.

The nominal full switching frequency of 132 kHz was chosen to minimize transformer size while keeping the fundamental EMI frequency below 150 kHz. The FREQUENCY pin (available only in TOP254-258 Y and E, L packages), when shorted to the CONTROL pin, lowers the full switching frequency to 66 kHz

Rev. H 06/13

9

TOP252-262

www.powerint.com

Figure 10. Switching Frequency Jitter (Idealized VDRAIN Waveforms).

PI-4

530-

0411

07

fOSC -

4 ms

Time

Switching Frequency

VDRAIN

fOSC +

(half frequency), which may be preferable in some cases such as noise sensitive video applications or a high efficiency standby mode. Otherwise, the FREQUENCY pin should be connected to the SOURCE pin for the default 132 kHz. In the M, P and G packages and the TOP259-261 Y package option, the full frequency PWM mode is set at 66 kHz, for higher efficiency and increased output power in all applications.

To further reduce the EMI level, the switching frequency in the full frequency PWM mode is jittered (frequency modulated) by approximately ±2.5 kHz for 66 kHz operation or ±5 kHz for 132 kHz operation at a 250 Hz (typical) rate as shown in Figure 10. The jitter is turned off gradually as the system is entering the variable frequency mode with a fixed peak drain current.

Pulse Width ModulatorThe pulse width modulator implements multi-mode control by driving the output MOSFET with a duty cycle inversely proportional to the current into the CONTROL pin that is in excess of the internal supply current of the chip (see Figure 9). The feedback error signal, in the form of the excess current, is filtered by an RC network with a typical corner frequency of 7 kHz to reduce the effect of switching noise in the chip supply current generated by the MOSFET gate driver.

To optimize power supply efficiency, four different control modes are implemented. At maximum load, the modulator operates in full frequency PWM mode; as load decreases, the modulator automatically transitions, first to variable frequency PWM mode, then to low frequency PWM mode. At light load, the control operation switches from PWM control to multi-cycle-modulation control, and the modulator operates in multi-cycle-modulation mode. Although different modes operate differently to make transitions between modes smooth, the simple relationship between duty cycle and excess CONTROL pin current shown in Figure 9 is maintained through all three PWM modes. Please see the following sections for the details of the operation of each mode and the transitions between modes.

Full Frequency PWM mode: The PWM modulator enters full frequency PWM mode when the CONTROL pin current (IC) reaches IB. In this mode, the average switching frequency is kept constant at fOSC (66 kHz for P, G and M packages and TOP259-261 Y, pin selectable 132 kHz or 66 kHz for Y and E/L

packages). Duty cycle is reduced from DCMAX through the reduction of the on-time when IC is increased beyond IB. This operation is identical to the PWM control of all other TOPSwitch families. TOPSwitch-HX only operates in this mode if the cycle-by-cycle peak drain current stays above kPS(UPPER)*ILIMIT(set), where kPS(UPPER) is 55% (typical) and ILIMIT(set) is the current limit externally set via the X or M pin.

Variable Frequency PWM mode: When peak drain current is lowered to kPS(UPPER)* ILIMIT(set) as a result of power supply load reduction, the PWM modulator initiates the transition to variable frequency PWM mode, and gradually turns off frequency jitter. In this mode, peak drain current is held constant at kPS(UPPER)* ILIMIT(set) while switching frequency drops from the initial full frequency of fOSC (132 kHz or 66 kHz) towards the minimum frequency of fMCM(MIN) (30 kHz typical). Duty cycle reduction is accomplished by extending the off-time.

Low Frequency PWM mode: When switching frequency reaches fMCM(MIN) (30 kHz typical), the PWM modulator starts to transition to low frequency mode. In this mode, switching frequency is held constant at fMCM(MIN) and duty cycle is reduced, similar to the full frequency PWM mode, through the reduction of the on-time. Peak drain current decreases from the initial value of kPS(UPPER)* ILIMIT(set) towards the minimum value of kPS(LOWER)*ILIMIT(set), where kPS(LOWER) is 25% (typical) and ILIMIT(set) is the current limit externally set via the X or M pin.

Multi-Cycle-Modulation mode: When peak drain current is lowered to kPS(LOWER)*ILIMIT(set), the modulator transitions to multi-cycle-modulation mode. In this mode, at each turn-on, the modulator enables output switching for a period of TMCM(MIN) at the switching frequency of fMCM(MIN) (4 or 5 consecutive pulses at 30 kHz) with the peak drain current of kPS(LOWER)*ILIMIT(set), and stays off until the CONTROL pin current falls below IC(OFF). This mode of operation not only keeps peak drain current low but also minimizes harmonic frequencies between 6 kHz and 30 kHz. By avoiding transformer resonant frequency this way, all potential transformer audible noises are greatly suppressed.

Maximum Duty CycleThe maximum duty cycle, DCMAX, is set at a default maximum value of 78% (typical). However, by connecting the VOLTAGE-MONITOR or MULTI-FUNCTION pin (depending on the package) to the rectified DC high voltage bus through a resistor with appropriate value (4 MW typical), the maximum duty cycle can be made to decrease from 78% to 40% (typical) when input line voltage increases from 88 V to 380 V, with dual gain slopes.

Error AmplifierThe shunt regulator can also perform the function of an error amplifier in primary side feedback applications. The shunt regulator voltage is accurately derived from a temperature-compensated bandgap reference. The CONTROL pin dynamic impedance ZC sets the gain of the error amplifier. The CONTROL pin clamps external circuit signals to the VC voltage level. The CONTROL pin current in excess of the supply current is separated by the shunt regulator and becomes the feedback current Ifb for the pulse width modulator.

Rev. H 06/13

10

TOP252-262

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On-Chip Current Limit with External Programmability The cycle-by-cycle peak drain current limit circuit uses the output MOSFET ON-resistance as a sense resistor. A current limit comparator compares the output MOSFET on-state drain to source voltage VDS(ON) with a threshold voltage. High drain current causes VDS(ON) to exceed the threshold voltage and turns the output MOSFET off until the start of the next clock cycle. The current limit comparator threshold voltage is temperature compensated to minimize the variation of the current limit due to temperature related changes in RDS(ON) of the output MOSFET. The default current limit of TOPSwitch-HX is preset internally. However, with a resistor connected between EXTERNAL CURRENT LIMIT (X) pin (Y, E/L and M packages) or MULTI-FUNCTION (M) pin (P and G package) and SOURCE pin (for TOP259-261 Y, the X pin is connected to the SIGNAL GROUND (G) pin), current limit can be programmed externally to a lower level between 30% and 100% of the default current limit. By setting current limit low, a larger TOPSwitch-HX than necessary for the power required can be used to take advantage of the lower RDS(ON) for higher efficiency/smaller heat sinking requirements. TOPSwitch-HX current limit reduction initial tolerance through the X pin (or M pin) has been improved significantly compare with previous TOPSwitch-GX. With a second resistor connected between the EXTERNAL CURRENT LIMIT (X) pin (Y, E/L and M packages) or MULTI-FUNCTION (M) pin (P and G package) and the rectified DC high voltage bus, the current limit is reduced with increasing line voltage, allowing a true power limiting operation against line variation to be implemented. When using an RCD clamp, this power limiting technique reduces maximum clamp voltage at high line. This allows for higher reflected voltage designs as well as reducing clamp dissipation.

The leading edge blanking circuit inhibits the current limit comparator for a short time after the output MOSFET is turned

on. The leading edge blanking time has been set so that, if a power supply is designed properly, current spikes caused by primary-side capacitances and secondary-side rectifier reverse recovery time should not cause premature termination of the switching pulse.

The current limit is lower for a short period after the leading edge blanking time. This is due to dynamic characteristics of the MOSFET. During startup and fault conditions the controller prevents excessive drain currents by reducing the switching frequency.

Line Undervoltage Detection (UV)At power up, UV keeps TOPSwitch-HX off until the input line voltage reaches the undervoltage threshold. At power down, UV prevents auto-restart attempts after the output goes out of regulation. This eliminates power down glitches caused by slow discharge of the large input storage capacitor present in applications such as standby supplies. A single resistor connected from the VOLTAGE-MONITOR pin (Y, E/L and M packages) or MULTI-FUNCTION pin (P and G packages) to the rectified DC high voltage bus sets UV threshold during power up. Once the power supply is successfully turned on, the UV threshold is lowered to 44% of the initial UV threshold to allow extended input voltage operating range (UV low threshold). If the UV low threshold is reached during operation without the power supply losing regulation, the device will turn off and stay off until UV (high threshold) has been reached again. If the power supply loses regulation before reaching the UV low threshold, the device will enter auto-restart. At the end of each auto-restart cycle (S15), the UV comparator is enabled. If the UV high threshold is not exceeded, the MOSFET will be disabled during the next cycle (see Figure 11). The UV feature can be disabled independent of the OV feature.

PI-4531-121206

S13 S12 S0 S15 S13 S12 S0 S15 S14 S13 S15S14 S14 5.8 V 4.8 V

S15

0 V

0 V

0 V

VLINE

VC

VDRAIN

VOUT

Note: S0 through S15 are the output states of the auto-restart counter

2 1 2 3 4

0 V

~ ~

~ ~

~ ~

~ ~ ~ ~

S0 S15

~ ~

~ ~

~ ~

~ ~

VUV

~ ~

~ ~

~ ~

~ ~

S12 ~ ~

Figure 11. Typical Waveforms for (1) Power Up (2) Normal Operation (3) Auto-Restart (4) Power Down.

Rev. H 06/13

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TOP252-262

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Line Overvoltage Shutdown (OV)The same resistor used for UV also sets an overvoltage threshold, which, once exceeded, will force TOPSwitch-HX to stop switching instantaneously (after completion of the current switching cycle). If this condition lasts for at least 100 ms, the TOPSwitch-HX output will be forced into off state. Unlike with TOPSwitch-GX, however, when the line voltage is back to normal with a small amount of hysteresis provided on the OV threshold to prevent noise triggering, the state machine sets to S13 and forces TOPSwitch-HX to go through the entire auto-restart sequence before attempting to switch again. The ratio of OV and UV thresholds is preset at 4.5, as can be seen in Figure 12. When the MOSFET is off, the rectified DC high voltage surge capability is increased to the voltage rating of the MOSFET (700 V), due to the absence of the reflected voltage and leakage spikes on the drain. The OV feature can be disabled independent of the UV feature.

In order to reduce the no-load input power of TOPSwitch-HX designs, the V-pin (or M-pin for P Package) operates at very low currents. This requires careful layout considerations when designing the PCB to avoid noise coupling. Traces and components connected to the V-pin should not be adjacent to any traces carrying switching currents. These include the drain,

clamp network, bias winding return or power traces from other converters. If the line sensing features are used, then the sense resistors must be placed within 10 mm of the V-pin to minimize the V-pin node area. The DC bus should then be routed to the line sense resistors. Note that external capacitance must not be connected to the V-pin as this may cause misoperation of the V pin related functions.

Hysteretic or Latching Output Overvoltage Protection (OVP)The detection of the hysteretic or latching output overvoltage protection (OVP) is through the trigger of the line overvoltage threshold. The V-pin or M-pin voltage will drop by 0.5 V, and the controller measures the external attached impedance immediately after this voltage drops. If IV or IM exceeds IOV(LS) (336 mA typical) longer than 100 ms, TOPSwitch-HX will latch into a permanent off state for the latching OVP. It only can be reset if VV or VM goes below 1 V or VC goes below the power-up-reset threshold (VC(RESET)) and then back to normal.

If IV or IM does not exceed IOV(LS) or exceeds no longer than 100 ms, TOPSwitch-HX will initiate the line overvoltage and the hysteretic OVP. Their behavior will be identical to the line overvoltage shutdown (OV) that has been described in detail in the previous section.

Voltage Monitor and External Current Limit Pin Table*

Figure Number 16 17 18 19 20 21 22 23 24 25 26 27 28

Three Terminal Operation 3

Line Undervoltage 3 3 3 3 3 3

Line Overvoltage 3 3 3 3 3 3

Line Feed-Forward (DCMAX) 3 3 3 3 3

Output Overvoltage Protection 3 3

Overload Power Limiting 3

External Current Limit 3 3 3 3 3

Remote ON/OFF 3 3 3

Device Reset 3

*This table is only a partial list of many VOLTAGE MONITOR and EXTERNAL CURRENT LIMIT Pin Configurations that are possible.

Table 2. VOLTAGE MONITOR (V) Pin and EXTERNAL CURRENT LIMIT (X) Pin Configuration Options.

Multi-Function Pin Table*

Figure Number 29 30 31 32 33 34 35 36 37 38 39 40

Three Terminal Operation 3

Line Undervoltage 3 3 3 3

Line Overvoltage 3 3 3 3

Line Feed-Forward (DCMAX) 3 3 3

Output Overvoltage Protection 3 3

Overload Power Limiting 3

External Current Limit 3 3 3 3

Remote ON/OFF 3 3 3

Device Reset 3

*This table is only a partial list of many MULTI-FUNCTIONAL Pin Configurations that are possible.

Table 3. MULTI-FUNCTION (M) Pin Configuration Options.

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Figure 12. MULTI-FUNCTION (P and G package). VOLTAGE MONITOR and EXTERNAL CURRENT LIMIT (Y, E/L and M package) Pin Characteristics.

-250 -200 -150 -100 -50 0 25 50 75 100 125 336

PI-4646-071708

Output MOSFET Switching

(Enabled)

(Disabled)

(Non-Latching) (Latching)

ILIMIT (Default)

DCMAX (78%)

Current Limit

M Pin

V Pin X Pin

Maximum Duty Cycle

VBG

I

I

I

I

IUV IREM(N) IOV IOV(LS)

Pin Voltage

Note: This figure provides idealized functional characteristics with typical performance values. Please refer to the parametric table and typical performance characteristics sections of the data sheet for measured data. For a detailed description of each functional pin operation refer to the Functional Description section of the data sheet.

X and V Pins (Y, E, L and M Packages) and M Pin (P and G Packages) Current (µA)

Disabled when supply output goes out of regulation

The circuit examples shown in Figures 41, 42 and 43 show a simple method for implementing the primary sensed over-voltage protection.

During a fault condition resulting from loss of feedback, output voltage will rapidly rise above the nominal voltage. The increase in output voltage will also result in an increase in the voltage at the output of the bias winding. A voltage at the output of the bias winding that exceeds of the sum of the voltage rating of the Zener diode connected from the bias winding output to the V-pin (or M-pin) and V-pin (or M-pin) voltage, will cause a current in excess of IV or IM to be injected into the V-pin (or M-pin), which will trigger the OVP feature.

The primary sensed OVP protection circuit shown in Figures 41, 42 and 43 is triggered by a significant rise in output voltage (and therefore bias winding voltage). If the power supply is operating under heavy load or low input line conditions when an open loop occurs, the output voltage may not rise significantly. Under these conditions, a latching shutdown will not occur until load or line conditions change. Nevertheless, the operation provides the desired protection by preventing significant rise in the output voltage when the line or load conditions do change. Primary side OVP protection with the TOPSwitch-HX in a typical application will prevent a nominal 12 V output from rising above approximately 20 V under open loop conditions. If greater accuracy is required, a secondary sensed OVP circuit is recommended.

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Line Feed-Forward with DCMAX ReductionThe same resistor used for UV and OV also implements line voltage feed-forward, which minimizes output line ripple and reduces power supply output sensitivity to line transients. Note that for the same CONTROL pin current, higher line voltage results in smaller operating duty cycle. As an added feature, the maximum duty cycle DCMAX is also reduced from 78% (typical) at a voltage slightly lower than the UV threshold to 36% (typical) at the OV threshold. DCMAX of 36% at high line was chosen to ensure that the power capability of the TOPSwitch-HX is not restricted by this feature under normal operation. TOPSwitch-HX provides a better fit to the ideal feed-forward by using two reduction slopes: -1% per mA for all bus voltage less than 195 V (typical for 4 MW line impedance) and -0.25% per mA for all bus voltage more than 195 V. This dual slope line feed-forward improves the line ripple rejection significantly compared with the TOPSwitch-GX.

Remote ON/OFFTOPSwitch-HX can be turned on or off by controlling the current into the VOLTAGE-MONITOR pin or out from the EXTERNAL CURRENT LIMIT pin (Y, E/L and M packages) and into or out from the MULTI-FUNCTION pin (P and G package, see Figure 12). In addition, the VOLTAGE-MONITOR pin has a 1 V threshold comparator connected at its input. This voltage threshold can also be used to perform remote ON/OFF control.

When a signal is received at the VOLTAGE-MONITOR pin or the EXTERNAL CURRENT LIMIT pin (Y, E/L and M packages) or the MULTI-FUNCTION pin (P and G package) to disable the output through any of the pin functions such as OV, UV and remote ON/OFF, TOPSwitch-HX always completes its current switching cycle before the output is forced off.

As seen above, the remote ON/OFF feature can also be used as a standby or power switch to turn off the TOPSwitch-HX and keep it in a very low power consumption state for indefinitely long periods. If the TOPSwitch-HX is held in remote off state for long enough time to allow the CONTROL pin to discharge to the internal supply undervoltage threshold of 4.8 V (approximately 32 ms for a 47 mF CONTROL pin capacitance), the CONTROL pin goes into the hysteretic mode of regulation. In this mode, the CONTROL pin goes through alternate charge and discharge cycles between 4.8 V and 5.8 V (see CONTROL pin operation section above) and runs entirely off the high voltage DC input, but with very low power consumption (160 mW typical at 230 VAC with M or X pins open). When the TOPSwitch-HX is remotely turned on after entering this mode, it will initiate a normal start-up sequence with soft-start the next time the CONTROL pin reaches 5.8 V. In the worst case, the delay from remote on to start-up can be equal to the full discharge/charge cycle time of the CONTROL pin, which is approximately 125 ms for a 47 mF CONTROL pin capacitor. This reduced consumption remote off mode can eliminate expensive and unreliable in-line mechanical switches. It also allows for microprocessor controlled turn-on and turn-off sequences that may be required in certain applications such as inkjet and laser printers.

Soft-StartThe 17 ms soft-start sweeps the peak drain current and switching frequency linearly from minimum to maximum value by operating through the low frequency PWM mode and the variable frequency mode before entering the full frequency mode. In addition to start-up, soft-start is also activated at each restart attempt during auto-restart and when restarting after being in hysteretic regulation of CONTROL pin voltage (VC), due to remote OFF or thermal shutdown conditions. This effectively minimizes current and voltage stresses on the output MOSFET, the clamp circuit and the output rectifier during start-up. This feature also helps minimize output overshoot and prevents saturation of the transformer during start-up.

Shutdown/Auto-RestartTo minimize TOPSwitch-HX power dissipation under fault conditions, the shutdown/auto-restart circuit turns the power supply on and off at an auto-restart duty cycle of typically 2% if an out of regulation condition persists. Loss of regulation interrupts the external current into the CONTROL pin. VC regulation changes from shunt mode to the hysteretic auto-restart mode as described in CONTROL pin operation section. When the fault condition is removed, the power supply output becomes regulated, VC regulation returns to shunt mode, and normal operation of the power supply resumes.

Hysteretic Over-Temperature ProtectionTemperature protection is provided by a precision analog circuit that turns the output MOSFET off when the junction temperature exceeds the thermal shutdown temperature (142 °C typical). When the junction temperature cools to below the lower hysteretic temperature point, normal operation resumes, thus providing automatic recovery. A large hysteresis of 75 °C (typical) is provided to prevent overheating of the PC board due to a continuous fault condition. VC is regulated in hysteretic mode, and a 4.8 V to 5.8 V (typical) triangular waveform is present on the CONTROL pin while in thermal shutdown.

Bandgap ReferenceAll critical TOPSwitch-HX internal voltages are derived from a temperature-compensated bandgap reference. This voltage reference is used to generate all other internal current references, which are trimmed to accurately set the switching frequency, MOSFET gate drive current, current limit, and the line OV/UV/OVP thresholds. TOPSwitch-HX has improved circuitry to maintain all of the above critical parameters within very tight absolute and temperature tolerances.

High-Voltage Bias Current SourceThis high-voltage current source biases TOPSwitch-HX from the DRAIN pin and charges the CONTROL pin external capacitance during start-up or hysteretic operation. Hysteretic operation occurs during auto-restart, remote OFF and over-temperature shutdown. In this mode of operation, the current source is switched on and off, with an effective duty cycle of approxi-mately 35%. This duty cycle is determined by the ratio of CONTROL pin charge (IC) and discharge currents (ICD1 and ICD2). This current source is turned off during normal operation when the output MOSFET is switching. The effect of the current source switching will be seen on the DRAIN voltage waveform as small disturbances and is normal.

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TOP252-262

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VBG + VT

1 VVREF

200 µA

400 µA

CONTROL (C)

(Voltage Sense)

(Positive Current Sense - Undervoltage,Overvoltage, ON/OFF, Maximum Duty

Cycle Reduction, Output Over-voltage Protection)

(Negative Current Sense - ON/OFF,Current Limit Adjustment)

PI-4714-071408

TOPSwitch-HX

VOLTAGE MONITOR (V)


Y, E/L and M Package

VBG + VT

VREF

200 µA

400 µA

CONTROL (C)

MULTI-FUNCTION (M)

(Positive Current Sense - Undervoltage,Overvoltage, Maximum Duty Cycle Reduction,

Output Overvoltage Protection)

(Negative Current Sense - ON/OFF,Current Limit Adjustment)

PI-4715-071408

TOPSwitch-HX

P and G Package

Figure 13a. VOLTAGE MONITOR (V) and EXTERNAL CURRENT LIMIT (X) Pin Input Simplified Schematic.

Figure 13b. MULTI-FUNCTION (M) Pin Input Simplified Schematic.

Rev. H 06/13

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TOP252-262

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Typical Uses of FREQUENCY (F) Pin

PI-2654-071700

DCInput

Voltage

+

-

D

S

CCONTROL

F

PI-2655-071700

DCInput

Voltage

+

-

D

S

CCONTROL

F

Figure 14. Full Frequency Operation (132 kHz). Figure 15. Half Frequency Operation (66 kHz).

Rev. H 06/13

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Typical Uses of VOLTAGE MONITOR (V) and EXTERNAL CURRENT LIMIT (X) Pins

X F

PI-4716-020508

DCInput

Voltage

+

-

DC S D

S

CCONTROL

V

V X C S F D

D S C

D C X V

S SS S S

TOP254-258YTOP252-258M

PI-4717-120307

DCInput

Voltage

+

-

D

S

CCONTROL

V

4 MΩRLS

VUV = IUV × RLS + VV (IV = IUV)VOV = IOV × RLS + VV (IV = IOV)

For RLS = 4 MΩ VUV = 102.8 VDC VOV = 451 VDC


PI-4756-121007

DCInput

Voltage

Sense Output Voltage

+

-

D V

S

C



DCMAX @ 100 VDC = 76%DCMAX @ 375 VDC = 41%

CONTROL

RLS 4 MΩ

10 kΩResetQR

PI-4719-120307

DCInput

Voltage


+

-

D V

S

C



DCMAX @ 100 VDC = 76% DCMAX @ 375 VDC = 41%

CONTROL

RLS 4 MΩ

ROVP >3kΩ

VROVPROVP

Figure 16a. Three Terminal Operation (VOLTAGE MONITOR and EXTERNAL CURRENT LIMIT Features Disabled. FREQUENCY Pin Tied to SOURCE or CONTROL Pin) for TOP254-258 Y Packages.

Figure 17. Line-Sensing for Undervoltage, Overvoltage and Line Feed-Forward.

Figure 18. Line-Sensing for Undervoltage, Overvoltage, Line Feed-Forward and Latched Output Overvoltage Protection.

Figure 19. Line-Sensing for Undervoltage, Overvoltage, Line Feed-Forward and Hysteretic Output Overvoltage Protection.

Figure 16c. Three Terminal Operation (VOLTAGE MONITOR and EXTERNAL CURRENT LIMIT Features Disabled. FREQUENCY Pin Tied to SOURCE or CONTROL Pin) for TOP252-262 L and E Packages.

X G

PI-4984-020708

DCInput

Voltage

+

-

D

C S D

S

CCONTROL

V

TOP259-261Y

V X C S G D

Figure 16b. Three Terminal Operation (VOLTAGE MONITOR and EXTERNAL CURRENT LIMIT Features Disabled for TOP259-261 Y Packages.

X F

DCInput

Voltage

+

-

DC S D

S

CCONTROL

V

V X C SF D

C S D

PI-4956-071708

eSIP E Package

V X C SF D

eSIP L Package

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TOP252-262

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PI-4720-120307

DCInput

Voltage

+

-

D V

S

C

VUV = RLS × IUV + VV (IV = IUV) For Values Shown VUV = 103.8 VDC

RLS

6.2 V

4 MΩ

40 kΩ

CONTROL

PI-4721-120307

DCInput

Voltage

+

-

D

S

CCONTROL

V

4 MΩ

55 kΩ

RLS

1N4148

VOV = IOV × RLS + VV (IV = IOV)

For Values Shown VOV = 457.2 VDC

Figure 20. Line Sensing for Undervoltage Only (Overvoltage Disabled). Figure 21. Line-Sensing for Overvoltage Only (Undervoltage Disabled). Maximum Duty Cycle Reduced at Low Line and Further Reduction with Increasing Line Voltage.

Typical Uses of VOLTAGE MONITOR (V) and EXTERNAL CURRENT LIMIT (X) Pins (cont.)

Figure 22. External Set Current Limit.

X

PI-4722-021308

DCInput

Voltage

+

-

D

S

C

RIL


See Figure 55b for other resistor values (RIL).

TOP259-261YN would use the G pin as the return for RIL.


CONTROL

X

PI-4723-011008

DCInput

Voltage

+

-

D

S

C

2.5 MΩRLS

6 kΩRIL

100% @ 100 VDC53% @ 300 VDC

ILIMIT =ILIMIT =


CONTROL

X

PI-2625-011008

DCInput

Voltage

+

-

D

S

C

ON/OFF47 KΩ

QR can be an optocoupler output or can be replaced by a manual switch.

TOP259-261YN would use the G pin as the return for QR.

QR

CONTROL

X

ON/OFF16 kΩ

PI-4724-011008

DCInput

Voltage

+

-

D

S

C

RIL QR

12 kΩFor RIL =

ILIMIT = 61%

19 kΩFor RIL =

ILIMIT = 37%


CONTROL


Figure 23. Current Limit Reduction with Line Voltage.

Figure 24. Active-on (Fail Safe) Remote ON/OFF. Figure 25. Active-on Remote ON/OFF with Externally Set Current Limit.

Rev. H 06/13

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TOP252-262

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Typical Uses of VOLTAGE MONITOR (V) and EXTERNAL CURRENT LIMIT (X) Pins (cont.)

PI-4727-061207

DCInput

Voltage

+

-

D

S

CCONTROL

M

D

S SS

D S C

S

CM

PI-4728-120307

DCInput

Voltage

+

-

D M

S

C

VUV = IUV × RLS + VM (IM = IUV)VOV = IOV × RLS + VM (IM = IOV)



CONTROL

RLS 4 MΩ

Figure 29. Three Terminal Operation (MULTI-FUNCTION Features Disabled). Figure 30. Line Sensing for Undervoltage, Overvoltage and Line Feed-Forward.

Figure 28. Line-Sensing for Undervoltage, Overvoltage, Line Feed-Forward and Latched Output Overvoltage Protection with Device Reset.

PI-4756-121007

DCInput

Voltage


+

-

D V

S

C




CONTROL

RLS 4 MΩ

10 kΩResetQR

Typical Uses of MULTI-FUNCTION (M) Pin

X

ON/OFF16 kΩ

PI-4725-011008

DCInput

Voltage

+

-

D

S

CCONTROL

V

RIL

RLS

QR

4 MΩ

VUV = IUV × RLS + VV (IV = IUV)VOV = IOV × RLS + VV (IV = IoV)


12 kΩFor RIL = ILIMIT = 61%



X

PI-

4726

-021

308

DCInput

Voltage

+

-

D

S

CCONTROL

V

RIL

RLS

12 kΩ

4 MΩ

VUV = IUV x RLS + VV (IV = IUV)VOV = IOV x RLS + VV (IV = IoV)

For RLS = 4 MΩ





Figure 26. Active-on Remote ON/OFF with Line-Sense and External Current Limit.

Figure 27. Line Sensing and Externally Set Current Limit.

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PI-4729-120307

DCInput

Voltage


+

-

D M

S

C




CONTROL

RLS 4 MΩ

Figure 31. Line Sensing for Undervoltage, Overvoltage, Line Feed-Forward and Latched Output Overvoltage Protection.

PI-4730-120307

DCInput

Voltage


+

-

D M

S

C




CONTROL

RLS 4 MΩ

VROVPROVP

ROVP >3kΩ

Figure 32. Line Sensing for Undervoltage, Overvoltage, Line Feed-Forward and Hysteretic Output Overvoltage Protection.

PI-4731-120307

DCInput

Voltage

+

-

D M

S

C

VUV = RLS × IUV + VM (IM = IUV) For Values Shown VUV = 103.8 VDC

RLS

6.2 V

4 MΩ

40 kΩ

CONTROL

PI-4732-120307

DCInput

Voltage

+

-

D M

S

C

VOV = IOV × RLS + VM (IM = IOV)

For Values Shown VOV = 457.2 VDC

CONTROL

RLS

1N4148

4 MΩ

55 kΩ

Figure 33. Line Sensing for Undervoltage Only (Overvoltage Disabled). Figure 34. Line Sensing for Overvoltage Only (Undervoltage Disabled). Maximum Duty Cycle Reduced at Low Line and Further Reduction with Increasing Line Voltage.

Typical Uses of MULTI-FUNCTION (M) Pin (cont.)

Figure 35. Externally Set Current Limit (Not Normally Required – See M Pin Operation Description).

PI-4733-021308

DCInput

Voltage

+

-

D M

S

C


CONTROLRIL

See Figures 55b for other resistor values (RIL) to select different ILIMIT values.


PI-4734-092107

DCInput

Voltage

+

-

D M

S

CCONTROLRIL

RLS 2.5 MΩ

6 kΩ

100% @ 100 VDC53% @ 300 VDC

ILIMIT =ILIMIT =

Figure 36. Current Limit Reduction with Line Voltage (Not Normally Required – See M Pin Operation Description).

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Typical Uses of MULTI-FUNCTION (M) Pin (cont.)

PI-4757-120307

DCInput

Voltage


+

-

D M

S

C

VUV = IUV × RLS + VM (IM = IUV) VOV = IOV × RLS + VM (IM = IOV)



CONTROL

RLS 4 MΩ

10 kΩQR

Reset

Figure 40. Line-Sensing for Undervoltage, Overvoltage, Line Feed-Forward and Latched Output Overvoltage Protection with Device Reset.

PI-4736-060607

DCInput

Voltage

+

-

D

S

CRIL

RMC 24 kΩ

12 kΩ

M

CONTROL

QR

2RILRMC =


ON/OFF7 kΩ

Figure 39. Active-off Remote ON/OFF with Externally Set Current Limit (see M Pin Operation Description).

PI-4735-092107

DCInput

Voltage

+

-

D

S

C

QR

RILM

CONTROL

12 kΩFor RIL =

ILIMIT = 61%


ON/OFF16 kΩ

19 kΩFor RIL =

ILIMIT = 37%

Figure 38. Active-on Remote ON/OFF with Externally Set Current Limit (see M Pin Operation Description).

PI-2519-040501

DCInput

Voltage

+

-

D

S

CQR

ON/OFF

M

CONTROL


47 kΩ

Figure 37. Active-on (Fail Safe) Remote ON/OFF.

Rev. H 06/13

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Application Examples

A High Efficiency, 35 W, Dual Output - Universal InputPower Supply The circuit in Figure 41 takes advantage of several of the TOPSwitch-HX features to reduce system cost and power supply size and to improve efficiency. This design delivers 35 W total continuous output power from a 90 VAC to 265 VAC input at an ambient of 50 ºC in an open frame configuration. A nominal efficiency of 84% at full load is achieved using TOP258P. With a DIP-8 package, this design provides 35 W continuous output power using only the copper area on the circuit board underneath the part as a heat sink. The different operating modes of the TOPSwitch-HX provide significant improvement in the no-load, standby, and light load performance of the power supply as compared to the previous generations of the TOPSwitch.

Resistors R3 and R4 provide line sensing, setting line UV at 100 VDC and line OV at 450 VDC.

Diode D5, together with resistors R6, R7, capacitor C6 and TVS VR1, forms a clamp network that limits the drain voltage of the TOPSwitch after the integrated MOSFET turns off. TVS VR1 provides a defined maximum clamp voltage and typically only conducts during fault conditions such as overload. This allows the RCD clamp (R6, R7, C6 and D5) to be sized for normal operation, thereby maximizing efficiency at light load. Should the feedback circuit fail, the output of the power supply may exceed regulation limits. This increased voltage at output will also result in an increased voltage at the output of the bias

winding. Zener VR2 will break down and current will flow into the “M” pin of the TOPSwitch initiating a hysteretic overvoltage protection with automatic restart attempts. Resistor R5 will limit the current into the M pin to < 336 mA, thus setting hysteretic OVP. If latching OVP is desired, the value of R5 can be reduced to 20 W.

The output voltage is controlled using the amplifier TL431. Diode D9, capacitor C20 and resistor R16 form the soft finish circuit. At startup, capacitor C20 is discharged. As the output voltage starts rising, current flows through the optocoupler diode inside U2A, resistor R13 and diode D9 to charge capacitor C20. This provides feedback to the circuit on the primary side. The current in the optocoupler diode U2A gradually decreases as the capacitor C20 becomes charged and the control amplifier IC U3 becomes operational. This ensures that the output voltage increases gradually and settles to the final value without any overshoot. Resistor R16 ensures that the capacitor C20 is maintained charged at all times after startup, which effectively isolates C20 from the feedback circuit after startup. Capacitor C20 discharges through R16 when the supply shuts down.

Resistors R20, R21 and R18 form a voltage divider network. The output of this divider network is primarily dependent on the divider circuit formed using R20 and R21 and will vary to some extent for changes in voltage at the 15 V output due to the connection of resistor R18 to the output of the divider network.Resistor R19 and Zener VR3 improve cross regulation in case only the 5 V output is loaded, which results in the 12 V output operating at the higher end of the specification.

Figure 41. 35 W Dual Output Power Supply using TOP258PN.

D

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C

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CONTROL

PI-4747-020508

R1133 Ω

R1233 Ω

R32.0 MΩ

R1610 kΩ

R1710 kΩ

R2110 kΩ

1%

R18196 kΩ

1%

R1910 Ω

R1422 ΩR13

330 Ω

R151 kΩ

R2012.4 kΩ

1%

D91N4148

U3TL431

2%

VR3BZX55B8V2

8.2 V2%

R720 Ω1/2 W

VR21N5250B

20 V

VR1P6KE200A

D5FR106

R42.0 MΩ

R55.1 kΩ

R11 MΩ

R21 MΩ

R86.8 Ω

R104.7 Ω

R622 kΩ2 W

U2BPS2501-

1-H-A

U2APS2501-

1-H-A

L23.3 µH

L16.8 mH

L33.3 µH

U1TOP258PN

C947 µF16 V C20

10 µF50 V

C21220 nF50 V

C191.0 µF50 V

C1010 µF50 V C11

2.2 nF250 VAC

D6FR106

D8 SB530

D7SB560

C8100 nF50 V

D11N4937

D21N4007

D31N4937

D41N4007

C13680 µF25 V

C14680 µF25 V

C15220 µF25 V

C18220 µF10 V

C172200 µF

10 V

C12470 pF100 V

C16470 pF100 V

2T1

EER28 7

11

9

3

6

5

4

C4100 µF400 V

C63.9 nF1 kV

C72.2 nF

250 VAC

C3220 nF

275 VAC

RT110 Ω

F13.15 A

TOPSwitch-HX

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+12 V,2 A

RTN

+5 V,2.2 A

RTN

tO

90 - 265VAC

Rev. H 06/13

22

TOP252-262

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A High Efficiency, 150 W, 250 – 380 VDC Input Power Supply The circuit shown in Figure 42 delivers 150 W (19 V @ 7.7 A) at 84% efficiency using a TOP258Y from a 250 VDC to 380 VDC input. A DC input is shown, as typically at this power level a power factor correction stage would precede this supply, providing the DC input. Capacitor C1 provides local decoupling, necessary when the supply is remote from the main PFC output capacitor.

The flyback topology is still usable at this power level due to the high output voltage, keeping the secondary peak currents low enough so that the output diode and capacitors are reasonably sized. In this example, the TOP258YN is at the upper limit of its power capability.

Resistors R3, R6 and R7 provide output power limiting, maintaining relatively constant overload power with input voltage. Line sensing is implemented by connecting a 4 MW resistor from the V pin to the DC rail. Resistors R4 and R5 together form the 4 MW line sense resistor. If the DC input rail rises above 450 VDC, then TOPSwitch-HX will stop switching until the voltage returns to normal, preventing device damage.

Due to the high primary current, a low leakage inductance transformer is essential. Therefore, a sandwich winding with a copper foil secondary was used. Even with this technique, the leakage inductance energy is beyond the power capability of a simple Zener clamp. Therefore, R1, R2 and C3 are added in parallel to VR1 and VR3, two series TVS diodes being used to reduce dissipation. During normal operation, very little power is

dissipated by VR1 and VR3, the leakage energy instead being dissipated by R1 and R2. However, VR1 and VR3 are essential to limit the peak drain voltage during start-up and/or overload conditions to below the 700 V rating of the TOPSwitch-HX MOSFET. The schematic shows an additional turn-off snubber circuit consisting of R20, R21, R22, D5 and C18. This reduces turn-off losses in the TOPSwitch-HX.

The secondary is rectified and smoothed by D2, D3 and C5, C6, C7 and C8. Two windings are used and rectified with separate diodes D2 and D3 to limit diode dissipation. Four capacitors are used to ensure their maximum ripple current specification is not exceeded. Inductor L1 and capacitors C15 and C16 provide switching noise filtering.

Output voltage is controlled using a TL431 reference IC and R15, R16 and R17 to form a potential divider to sense the output voltage. Resistor R12 and R24 together limit the optocoupler LED current and set overall control loop DC gain. Control loop compensation is achieved using components C12, C13, C20 and R13. Diode D6, resistor R23 and capacitor C19 form a soft finish network. This feeds current into the control pin prior to output regulation, preventing output voltage overshoot and ensuring startup under low line, full load conditions.

Sufficient heat sinking is required to keep the TOPSwitch-HX device below 110 °C when operating under full load, low line and maximum ambient temperature. Airflow may also be required if a large heat sink area is not acceptable.

L1

D41N4148

C11100 nF50 V

+19 V, 7.7 A

RTN

RT15 Ω

R194.7 Ω

D3MBR20100CTR7

4.7 MΩ

D2MBR20100CT

C15-C16820 µF25 V

C1447 pF1 kV

R201.5 kΩ2 W

C1047 µF10 V

D1BYV26C

T1EI35

11

4

13,14

5

12

1

9,10

7

R154.75 kΩ

1%

C201.0 µF50 V

C1747 pF1 kV

C910 µF50 V

R2315 kΩ

0.125 W

R1422 Ω

0.5 W

R38.06 kΩ

1%

C4

2.2 nF250 VAC

R106.8 Ω

C34.7 nF1 kV

C122 µF400 V

R221.5 kΩ

2 W

D61N4148

R84.7

R168 kΩ2 W

F14 A

C18120 pF1 kV

R1631.6 kΩ

1%

R268 kΩ

2 W

VR21N5258B

36 V

R111 kΩ

0.125 W

C1910 µF50 V

R12240 Ω

0.125 W

U1TOP258YN

R2430 Ω

0.125 W

C5-C8

25 V

VR1, VR3P6KE100A

R1822 Ω0.5 W

R21

2 W

D51N4937

U2PC817A

U3TL431

2%

C124.7 nF50 V

R17562 Ω1%

R1356 kΩ

0.125 W

C13100 nF

50 V

Ω

U2PC817B

3.3 µHR4

2.0 MΩ

R52.0 ΜΩ

1.5 kΩ

tO

TOPSwitch-HX

R64.7 MΩ

820 µF 250 - 380

VDC

PI-4795-092007

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Figure 42. 150 W, 19 V Power Supply using TOP258YN.

Rev. H 06/13

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TOP252-262

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A High Efficiency, 20 W continuous – 80 W Peak, UniversalInput Power Supply The circuit shown in Figure 43 takes advantage of several of TOPSwitch-HX features to reduce system cost and power supply size and to improve power supply efficiency while delivering significant peak power for a short duration. This design delivers continuous 20 W and peak 80 W at 32 V from an 90 VAC to 264 VAC input. A nominal efficiency of 82% at full load is achieved using TOP258MN. The M-package part has an optimized current limit to enable design of power supplies capable of delivering high power for a short duration.

Resistor R12 sets the current limit of the part. Resistors R11 and R14 provide line feed forward information that reduces the current limit with increasing DC bus voltage, thereby maintaining a constant overload power level with increasing line voltage. Resistors R1 and R2 implement the line undervoltage and overvoltage function and also provide feed forward compensation for reducing line frequency ripple at the output. The overvoltage feature inhibits TOPSwitch-HX switching during a line surge extending the high voltage withstand to 700 V without device damage.

The snubber circuit comprising of VR7, R17, R25, C5 and D2 limits the maximum drain voltage and dissipates energy stored in the leakage inductance of transformer T1. This clamp configuration maximizes energy efficiency by preventing C5 from discharging below the value of VR7 during the lower frequency operating modes of TOPSwitch-HX. Resistor R25 damps high frequency ringing for reduced EMI.

A combined output overvoltage and over power protection circuit is provided via the latching shutdown feature of

TOPSwitch-HX and R20, C9, R22 and VR5. Should the bias winding output voltage across C13 rise due to output overload or an open loop fault (opto coupler failure), then VR5 conducts triggering the latching shutdown. To prevent false triggering due to short duration overload, a delay is provided by R20, R22 and C9.

To reset the supply following a latching shutdown, the V pin must fall below the reset threshold. To prevent the long reset delay associated with the input capacitor discharging, a fast AC reset circuit is used. The AC input is rectified and filtered by D13 and C30. While the AC supply is present, Q3 is on and Q1 is off, allowing normal device operation. However when AC is removed, Q1 pulls down the V pin and resets the latch. The supply will then return to normal operation when AC is again applied.

Transistor Q2 provides an additional lower UV threshold to the level programmed via R1, R2 and the V pin. At low input AC voltage, Q2 turns off, allowing the X pin to float and thereby disabling switching.

A simple feedback circuit automatically regulates the output voltage. Zener VR3 sets the output voltage together with the voltage drop across series resistor R8, which sets the DC gain of the circuit. Resistors R10 and C28 provide a phase boost to improve loop bandwidth.

Diodes D6 and D7 are low-loss Schottky rectifiers, and capacitor C20 is the output filter capacitor. Inductor L3 is a common mode choke to limit radiated EMI when long output cables are used and the output return is connected to safety earth ground. Example applications where this occurs include PC peripherals, such as inkjet printers.

C81 nF

250 VAC

D6-D7

C91 µF

100 V

R171 kΩ0.5 W

VR7BZY97C150

150 V

T1

D2FR107

D131N4007

F13.15 A

C30100 nF400 V Q3

2N3904

R23

1 MΩ

C1220 nF

275 VAC

90 - 264 VAC

R24

1 MΩ

L15.3 mH

68 kΩ

D101N4007

C3120 µF400 V

R113.6 MΩ

D81N4007

RT110 Ω

R12 MΩ

R143.6 MΩ

D91N4007

Q22N3904

R1839 kΩ

Q12N3904

R22 MΩ

R32 MΩ

R151 kΩ

R211 MΩ

0.125 WR42 MΩ

R26

C

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D V

X

R222 MΩ

C6100 nF50 V

U4TOP258MN

C747 µF16 V

VR51N5250B

20 V

R25

C510 nF1 kV

R66.8 Ω

C101 nF

250 VAC

EF25

R20130 kΩ

D5LL4148

C1310 µF50 V

U2APC817D

R92 kΩ

R81.5 kΩ

R1056 Ω

VR31N5255B

28 V

C28330 nF50 V

R1968 Ω0.5 W

STPS3150

C26100 pF1 kV

L3

47 µH

L2

3.3 µH

C3122 µF50 V

C20330 µF

50 V

R127.5 kΩ

1%

D111N4007

100 Ω

CONTROL

C29220 nF50 V

to

32 V625 mA, 2.5 APK

RTN

PI-4833-092007

1

9

10

5

2

3

4

NC

TOPSwitch-HX

Figure 43. 20 W Continuous, 80 W Peak, Universal Input Power Supply using TOP258MN.

Rev. H 06/13

24

TOP252-262

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A High Efficiency, 65 W, Universal Input Power Supply The circuit shown in Figure 44 delivers 65 W (19 V @ 3.42 A) at 88% efficiency using a TOP260EN operating over an input voltage range of 90 VAC to 265 VAC.

Capacitors C1 and C6 and inductors L1 and L2 provide common mode and differential mode EMI filtering. Capacitor C2 is the bulk filter capacitor that ensures low ripple DC input to the flyback converter stage. Capacitor C4 provides decoupling for switching currents reducing differential mode EMI.

In this example, the TOP260EN is used at reduced current limit to improve efficiency.

Resistors R5, R6 and R7 provide power limiting, maintaining relatively constant overload power with input voltage. Line sensing is implemented by connecting a 4 MW impedance from the V pin to the DC rail. Resistors R3 and R4 together form the 4 MW line sense resistor. If the DC input rail rises above 450 VDC, then TOPSwitch-HX will stop switching until the voltage returns to normal, preventing device damage.

This circuit features a high efficiency clamp network consisting of diode D1, zener VR1, capacitor C5 together with resistors R8 and R9. The snubber clamp is used to dissipate the energy of the leakage reactance of the transformer. At light load levels, very little power is dissipated by VR1 improving efficiency as compared to a conventional RCD clamp network.

The secondary output from the transformer is rectified by diode D2 and filtered by capacitors C13 and C14. Ferrite Bead L3 and capacitors C15 form a second stage filter and effectively reduce the switching noise to the output.

Output voltage is controlled using a LM431 reference IC. Resistor R19 and R20 form a potential divider to sense the output voltage. Resistor R16 limits the optocoupler LED current and sets the overall control loop DC gain. Control loop compensation is achieved using C18 and R21. The components connected to the control pin on the primary side C8, C9 and R15 set the low frequency pole and zero to further shape the control loop response. Capacitor C17 provides a soft finish during startup. Optocoupler U2 is used for isolation of the feedback signal.

Diode D4 and capacitor C10 form the bias winding rectifier and filter. Should the feedback loop break due to a defective component, a rising bias winding voltage will cause the Zener VR2 to break down and trigger the over voltage protection which will inhibit switching.

An optional secondary side over voltage protection feature which offers higher precision (as compared to sensing via the bias winding) is implemented using VR3, R18 and U3. Excess voltage at the output will cause current to flow through the optocoupler U3 LED which in turn will inject current in the V-pin through resistor R13, thereby triggering the over voltage protection feature.

Figure 44. 65 W, 19 V Power Supply Using TOP260EN.

PI-4998-021408

R1633 Ω

R211 kΩ

R2010 kΩ

R1968.1 kΩ

R1847 Ω

R16680 Ω

U4LM431

2%

VR3BZX79-C22

22 VD1

DL4937

D61N4148

D3BAV19WS

D5BAV19WS

VR21N5248B

18 V

VR1BZY97C180

180 V

R135.1 Ω

R14100 Ω

R125.1 kΩ

R112 MΩ

R12.2 MΩ

R22.2 MΩ

R156.8 Ω

R1073.2 kΩ

R8100 Ω

R91 kΩ

U3BPC357A

U3APC357A

U2BLTY817C

U2ALTY817C

L3FerriteBead

L112 mH

L2Ferrite Bead

U1TOP260EN

C947 µF16 V

C161 µF50 V

C1733 µF35 V

C18100 nF

C11100 nF50 V

C1022 µF50 V

D4 BAV19WS

D2MBR20100CT

C8100 nF50 V

C4100 nF400 V

3KBP08MBR1

C13470 µF25 V

C14470 µF25 V

C1547 µF25 V

C121 nF

100 V

4T1

RM10 FL1

FL25

3

2

6

C62.2 nF

250 VAC

C1330 nF

275 VACF14 A TOPSwitch-HX

L

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19 V, 3.42 A

RTN

C2120 µF400 V

C3470 pF

250 VAC

C7100 nF25 V

C52.2 nF1 kV

90 - 265VAC

D

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FX

CONTROL

R32.0 MΩ

R55.1 MΩ

R42.0 MΩ

R715 kΩ

1%

R66.8 MΩ

Rev. H 06/13

25

TOP252-262

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Key Application Considerations

TOPSwitch-HX vs. TOPSwitch-GX

Table 4 compares the features and performance differences between TOPSwitch-HX and TOPSwitch-GX. Many of the new

features eliminate the need for additional discrete components. Other features increase the robustness of design, allowing cost savings in the transformer and other power components.

TOPSwitch-HX vs. TOPSwitch-GX

Function TOPSwitch-GX TOPSwitch-HX TOPSwitch-HX Advantages

EcoSmart Linear frequency reduction to 30 kHz (@ 132 kHz) for duty cycles < 10%

Multi-mode operation with linear frequency reduction to 30 kHz (@ 132 kHz) and multi-cycle modulation (virtually no audible noise)

• Improved efficiency over load (e.g. at 25% load point)

• Improved standby efficiency• Improved no-load consumption

Output Overvoltage Protection (OVP)

Not available User programmable primary or secondary hysteretic or latching OVP

• Protects power supply output during open loop fault• Maximum design flexibility

Line Feed-Forward with Duty Cycle Reduction

Linear reduction Dual slope reduction with lower, more accurate onset point

• Improved line ripple rejection• Smaller DC bus capacitor

Switching Frequency DIP-8 Package

132 kHz 66 kHz • Increased output power for given MOSFET size due to higher efficiency

Lowest MOSFET On Resistance in DIP-8 Package

3.0 W (TOP246P) 1.8 W (TOP258P) • Increased output power in designs without external heat sink

I2f Trimming Not available -10% / +20% • Increased output power for given core size• Reduced over-load power

Auto-restart Duty Cycle 5.6% 2% • Reduced delivered average output power during open loop faults

Frequency Jitter ±4 kHz @ 132 kHz ±2 kHz @ 66 kHz

±5 kHz @ 132 kHz ±2.5 kHz @ 66 kHz

• Reduced EMI filter cost

Thermal Shutdown 130 °C to 150 °C 135 °C to 150 °C • Increased design margin

External Current Limit 30%-100% of ILIMIT 30%-100% of ILIMIT, additional trim at 0.7 × ILIMIT

• Reduced tolerances when current limit is set externally

Line UV Detection Threshold 50 mA (2 MW sense impedance)

25 mA (4 MW sense impedance)

• Reduced dissipation for lower no-load consumption

Soft-Start 10 ms duty cycle and current limit ramp

17 ms sweep through multi-mode characteristic

• Reduced peak current and voltage component stress at startup

• Smooth output voltage rise

Table 4. Comparison Between TOPSwitch-GX and TOPSwitch-HX.

Rev. H 06/13

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TOP252-262

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TOPSwitch-HX Design Considerations

Power TableThe data sheet power table (Table 1) represents the maximum practical continuous output power based on the following conditions: 1. 12 V output.2. Schottky or high efficiency output diode. 3. 135 V reflected voltage (VOR) and efficiency estimates. 4. A 100 VDC minimum for 85-265 VAC and 250 VDC mini-

mum for 230 VAC.5. Sufficient heat sinking to keep device temperature ≤100 °C. 6. Power levels shown in the power table for the M/P package

device assume 6.45 cm2 of 610 g/m2 copper heat sink area in an enclosed adapter, or 19.4 cm2 in an open frame.

The provided peak power depends on the current limit for the respective device.

TOPSwitch-HX SelectionSelecting the optimum TOPSwitch-HX depends upon required maximum output power, efficiency, heat sinking constraints, system requirements and cost goals. With the option to externally reduce current limit, an Y, E/L or M package TOPSwitch-HX may be used for lower power applications where higher efficiency is needed or minimal heat sinking is available.

Input CapacitorThe input capacitor must be chosen to provide the minimum DC voltage required for the TOPSwitch-HX converter to maintain regulation at the lowest specified input voltage and maximum output power. Since TOPSwitch-HX has a high DCMAX limit and an optimized dual slope line feed forward for ripple rejection, it is possible to use a smaller input capacitor. For TOPSwitch-HX, a capacitance of 2 mF per watt is possible for universal input with an appropriately designed transformer.

Primary Clamp and Output Reflected Voltage VOR

A primary clamp is necessary to limit the peak TOPSwitch-HX drain to source voltage. A Zener clamp requires few parts and takes up little board space. For good efficiency, the clamp Zener should be selected to be at least 1.5 times the output reflected voltage VOR, as this keeps the leakage spike conduction time short. When using a Zener clamp in a universal input application, a VOR of less than 135 V is recommended to allow for the absolute tolerances and temperature variations of the Zener. This will ensure efficient operation of the clamp circuit and will also keep the maximum drain voltage below the rated breakdown voltage of the TOPSwitch-HX MOSFET. A high VOR is required to take full advantage of the wider DCMAX of TOPSwitch-HX. An RCD clamp provides tighter clamp voltage tolerance than a Zener clamp and allows a VOR as high as 150 V. RCD clamp dissipation can be minimized by reducing the external current limit as a function of input line voltage (see Figures 23 and 36). The RCD clamp is more cost effective than the Zener clamp but requires more careful design (see Quick Design Checklist).

Output DiodeThe output diode is selected for peak inverse voltage, output current, and thermal conditions in the application (including heat

sinking, air circulation, etc.). The higher DCMAX of TOPSwitch-HX, along with an appropriate transformer turns ratio, can allow the use of a 80 V Schottky diode for higher efficiency on output voltages as high as 15 V (see Figure 41).

Bias Winding CapacitorDue to the low frequency operation at no-load, a 10 mF bias winding capacitor is recommended.

Soft-StartGenerally, a power supply experiences maximum stress at start-up before the feedback loop achieves regulation. For a period of 17 ms, the on-chip soft-start linearly increases the drain peak current and switching frequency from their low starting values to their respective maximum values. This causes the output voltage to rise in an orderly manner, allowing time for the feedback loop to take control of the duty cycle. This reduces the stress on the TOPSwitch-HX MOSFET, clamp circuit and output diode(s), and helps prevent transformer saturation during start-up. Also, soft-start limits the amount of output voltage overshoot and, in many applications, eliminates the need for a soft-finish capacitor.

EMIThe frequency jitter feature modulates the switching frequency over a narrow band as a means to reduce conducted EMI peaks associated with the harmonics of the fundamental switching frequency. This is particularly beneficial for average detection mode. As can be seen in Figure 45, the benefits of jitter increase with the order of the switching harmonic due to an increase in frequency deviation. Devices in the P, G or M package and TOP259-261YN operate at a nominal switching frequency of 66 kHz. The FREQUENCY pin of devices in the TOP254-258 Y and E packages offer a switching frequency option of 132 kHz or 66 kHz. In applications that require heavy snubber on the drain node for reducing high frequency radiated noise (for example, video noise sensitive applications such as VCRs, DVDs, monitors, TVs, etc.), operating at 66 kHz will reduce snubber loss, resulting in better efficiency. Also, in applications where transformer size is not a concern, use of the 66 kHz option will provide lower EMI and higher efficiency. Note that the second harmonic of 66 kHz is still below 150 kHz, above which the conducted EMI specifications get much tighter. For 10 W or below, it is possible to use a simple inductor in place of a more costly AC input common mode choke to meet worldwide conducted EMI limits.

Transformer DesignIt is recommended that the transformer be designed for maximum operating flux density of 3000 Gauss and a peak flux density of 4200 Gauss at maximum current limit. The turns ratio should be chosen for a reflected voltage (VOR) no greater than 135 V when using a Zener clamp or 150 V (max) when using an RCD clamp with current limit reduction with line voltage (overload protection). For designs where operating current is significantly lower than the default current limit, it is recommended to use an externally set current limit close to the operating peak current to reduce peak flux density and peak power (see Figures 22 and 35). In most applications, the tighter current limit tolerance, higher switching frequency and soft-start features of TOPSwitch-HX contribute to a smaller transformer when compared to TOPSwitch-GX.

Rev. H 06/13

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TOP252-262

www.powerint.com

Figure 45b. TOPSwitch-HX Full Range EMI Scan (132 kHz With Jitter) With Identical Circuitry and Conditions.

-20

-10

0

-10

20

30

40

50

60

70

80

0.15 1 10 30

Frequency (MHz)

Am

plit

ud

e (d

BµV

)

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EN55022B (QP)EN55022B (AV)

EN55022B (QP)EN55022B (AV)

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600

TOPSwitch-HX (with jitter)

Figure 45a. Fixed Frequency Operation Without Jitter.

Standby ConsumptionFrequency reduction can significantly reduce power loss at light or no load, especially when a Zener clamp is used. For very low secondary power consumption, use a TL431 regulator for feedback control. A typical TOPSwitch-HX circuit automatically enters MCM mode at no load and the low frequency mode at light load, which results in extremely low losses under no-load or standby conditions.

High Power DesignsThe TOPSwitch-HX family contains parts that can deliver up to 333 W. High power designs need special considerations. Guidance for high power designs can be found in the Design Guide for TOPSwitch-HX (AN-43).

TOPSwitch-HX Layout Considerations

The TOPSwitch-HX has multiple pins and may operate at high power levels. The following guidelines should be carefully followed.

Primary Side ConnectionsUse a single point (Kelvin) connection at the negative terminal of the input filter capacitor for the TOPSwitch-HX SOURCE pin and bias winding return. This improves surge capabilities by returning surge currents from the bias winding directly to the input filter capacitor. The CONTROL pin bypass capacitor should be located as close as possible to the SOURCE and CONTROL pins, and its SOURCE connection trace should not be shared by the main MOSFET switching currents. All SOURCE pin referenced components connected to the MULTI-FUNCTION (M-pin), VOLTAGE MONITOR (V-pin) or EXTERNAL CURRENT LIMIT (X-pin) pins should also be located closely between their respective pin and SOURCE. Once again, the SOURCE connection trace of these components should not be shared by the main MOSFET switching currents. It is very critical that SOURCE pin switching currents are returned to the input capacitor negative terminal through a separate trace that is not shared by the components connected to CONTROL, MULTI-FUNCTION, VOLTAGE MONITOR or EXTERNAL CURRENT LIMIT pins. This is because the SOURCE pin is also the controller ground reference pin. Any traces to the M, V, X or C pins should be kept as short as possible and away from the DRAIN trace to prevent noise coupling. VOLTAGE MONITOR resistors (R1 and R2 in Figures 46, 47, 48, R3 and R4 in Figure 49, and R14 in Figure 50) should be located close to the M or V pin to minimize the trace length on the M or V pin side. Resistors connected to the M, V or X pin should be connected as close to the bulk cap positive terminal as possible while routing these connections away from the power switching circuitry. In addition to the 47 μF CONTROL pin capacitor, a high frequency bypass capacitor in parallel may be used for better noise immunity. The feedback optocoupler output should also be located close to the CONTROL and SOURCE pins of TOPSwitch-HX and away from the drain and clamp component traces.

Y CapacitorThe Y capacitor should be connected close to the secondary output return pin(s) and the positive primary DC input pin of the transformer.

Heat SinkingThe tab of the Y package (TO-220C) and E package (eSIP-7C) and L package (eSIP-7F) are internally electrically tied to the SOURCE pin. To avoid circulating currents, a heat sink attached to the tab should not be electrically tied to any primary ground/source nodes on the PC board. When using a P (DIP-8), G (SMD-8) or M (DIP-10) package, a copper area underneath the package connected to the SOURCE pins will act as an effective heat sink. On double sided boards, topside and bottom side areas connected with vias can be used to increase the effective heat sinking area. In addition, sufficient copper area should be provided at the anode and cathode leads of the output diode(s) for heat sinking. In Figures 46 to 50 a narrow trace is shown between the output rectifier and output filter capacitor. This trace acts as a thermal relief between the rectifier and filter capacitor to prevent excessive heating of the capacitor.

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Figure 46. Layout Considerations for TOPSwitch-HX Using P Package.

Figure 47. Layout Considerations for TOPSwitch-HX Using M Package.

+- DCOut

+

-

HV

PI-4753-070307

Y1-Capacitor

C6

Isolation Barrier

OutputRectifier

R1 R2

JP1

J1

C1U1

R3

C2R4

D1

VR1

C4C3R8

D2

VR2

C5

C9

D3C7

L1

C8

J2

R8

R13 R14R6

R7

JP2

R12

R11

R10U3

R9C10

T1

Output FilterCapacitor

Input FilterCapacitor

Maximize hatched copper areas ( ) for optimum heat sinking

U2

Transformer

DSS

SS

CM

Optional PCB slot for external heatsink in contact with

SOURCE pins

+- DCOut

+

-HV

PI-4752-070307

Isolation Barrier

OutputRectifier

R1

JP1

J1

C1U1

R5

C2

R6

D1

VR1

C4R7

C3R8

R9D2

C5

D3C7

L1

C8

J2R11R

10

JP2

C9

R15U3

R16R17

R14

R12

T1

R13

VR2

R2R3 R4



Optional PCB slot for external heatsink in contact with

SOURCE pins

Maximize hatched copper areas ( ) for optimum heat sinking

SS D

CXV

SSS

U2

Y1-Capacitor

C6

Transformer

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Figure 48. Layout Considerations for TOPSwitch-HX Using TOP254-258 Y Package.

+- DCOut

+

-HV

PI-4751-070307

Y1-Capacitor

C6

Isolation Barrier

OutputRectifier

R1 R2

R3 R4

JP1

J1

C1

U1

HS1

R3

C2R4

D1

VR1

C4R7 R10

R13

D2

VR2

C5 C9

D3

C7

L1

C8

J2R

9

R11 R16 R

14

R8

JP2

R12R17R15

U3

R12C10

T1



Transformer

S F

C

X V

D

U2

Figure 49. Layout Considerations for TOPSwitch-HX Using TOP259-261 Y Package.

+

-HV

+- DCOut

PI-4977-021408

Y1-Capacitor

C7

Isolation Barrier

J1

J2

C4 HS1

R3

R22R14 R8

C9

C8

U5

D5

R7C6

R6VR1

R9

R5VR2

R10

D6 C10

JP2

R11

R4L3C17

D8

R12C16

R15

U4 C21

R17R13

R21

R20C18

JP1

U2

T1



Transformer

CG

D

V

S

X

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+- DCOut

+

-HV

PI-4975-022108

Y1-Capacitor

C7

Isolation Barrier

OutputRectifier

R4

R3

R11

R5

U1

C9

R22R8

R14D6

C10

R10

JP2U2

U4

HS1

R17

C21

R13R15 R21

R9

VR2

R6 D5

R7

VR1

C6

C4

C8

H52

C17

C18

R20

L3

C19

D8

C16 R12T1



Transformer

J1

J2

XF

D

C

S

V

Figure 50a. Layout Considerations for TOPSwitch-HX Using E Package and Operating at 66 kHz.

+

-HV

+- DCOut PI-4976-011410

Y1-Capacitor

C7

Isolation Barrier

T1

OutputRectifier

R4

R3

R11

R5

J1

J2

U1

R6D5

C6 R7

R8

C8

R22

D6C10

R10

R9VR2

C9

R14

VR1

HS1C4

U2

R15R13

R17

JP2

U4

C21

R21

R20C19

L3

H52D8

C16 R12

C18

C17



Transformer

XF

D

C

S

V

Figure 50b. Layout Considerations for TOPSwitch-HX Using E Package and Operating at 132 kHz.

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TOP252-262

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Quick Design Checklist

In order to reduce the no-load input power of TOPSwitch-HX designs, the V-pin (or M-pin for P Package) operates at very low current. This requires careful layout considerations when designing the PCB to avoid noise coupling. Traces and components connected to the V-pin should not be adjacent to any traces carrying switching currents. These include the drain, clamp network, bias winding return or power traces from other converters. If the line sensing features are used, then the sense resistors must be placed within 10 mm of the V-pin to minimize the V pin node area. The DC bus should then be routed to the line sense resistors. Note that external capacitance must not be connected to the V-pin as this may cause misoperation of the V pin related functions.

As with any power supply design, all TOPSwitch-HX designs should be verified on the bench to make sure that components specifications are not exceeded under worst-case conditions. The following minimum set of tests is strongly recommended:

1. Maximum drain voltage – Verify that peak VDS does not exceed 675 V at highest input voltage and maximum overload output power. Maximum overload output power occurs when the output is overloaded to a level just before the power supply goes into auto-restart (loss of regulation).

2. Maximum drain current – At maximum ambient temperature, maximum input voltage and maximum output load, verify

drain current waveforms at start-up for any signs of trans-former saturation and excessive leading edge current spikes. TOPSwitch-HX has a leading edge blanking time of 220 ns to prevent premature termination of the ON-cycle. Verify that the leading edge current spike is below the allowed current limit envelope (see Figure 53) for the drain current waveform at the end of the 220 ns blanking period.

3. Thermal check – At maximum output power, both minimum and maximum voltage and ambient temperature; verify that temperature specifications are not exceeded for TOPSwitch-HX, transformer, output diodes and output capacitors. Enough thermal margin should be allowed for the part-to-part variation of the RDS(ON) of TOPSwitch-HX, as specified in the data sheet. The margin required can either be calculated from the values in the parameter table or it can be accounted for by connecting an external resistance in series with the DRAIN pin and attached to the same heat sink, having a resistance value that is equal to the difference between the measured RDS(ON) of the device under test and the worst case maximum specification.

Design Tools

Up-to-date information on design tools can be found at the Power Integrations website: www.powerint.com

Figure 50c. Layout Considerations for TOPSwitch-HX Using L Package and Operating at 132 kHz.

+- DCOut

+

-HV

PI-5216-091508

Y1-Capacitor

C7

Isolation Barrier

OutputRectifier

J1

R11

R3

R4

R5

R14

JP1

C4 R6

D5

C6

R7

VR1

R22

C8

R8U1

C9

D6C10

R10

VR2R9

JP2

R15

R13

R17

U4

C21

R21

D8

C16R12

HS2

HS1

C17

J2

R20

C19

L3

C18

T1



Note: Components U1, R8, C8, C9 and R22 are under heat sink HS1.

Transformer

X F DY SC

U2

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Absolute Maximum Ratings(2)

DRAIN Peak Voltage ........................................... -0.3 V to 700 V DRAIN Peak Current: TOP252 ......................................... 0.68 A DRAIN Peak Current: TOP253 ......................................... 1.37 A DRAIN Peak Current: TOP254 ......................................... 2.08 ADRAIN Peak Current: TOP255 ......................................... 2.72 A DRAIN Peak Current: TOP256 ......................................... 4.08 A DRAIN Peak Current: TOP257 ......................................... 5.44 ADRAIN Peak Current: TOP258 ......................................... 6.88 ADRAIN Peak Current: TOP259 ......................................... 7.73 ADRAIN Peak Current: TOP260 ......................................... 9.00 ADRAIN Peak Current: TOP261 ....................................... 11.10 ADRAIN Peak Current: TOP262 ....................................... 11.10 A CONTROL Voltage ................................................. -0.3 V to 9 V CONTROL Current ........................................................ 100 mA

VOLTAGE MONITOR Pin Voltage ........................... -0.3 V to 9 V CURRENT LIMIT Pin Voltage .............................. -0.3 V to 4.5 V MULTI-FUNCTION Pin Voltage ............................... -0.3 V to 9 V FREQUENCY Pin Voltage ...................................... -0.3 V to 9 V Storage Temperature ...................................... -65 °C to 150 °C Operating Junction Temperature ......................-40 °C to 150 °C Lead Temperature(1) ........................................................260 °C Notes: 1. 1/16 in. from case for 5 seconds. 2. Maximum ratings specified may be applied one at a time without causing permanent damage to the product. Exposure to Absolute Maximum Rating conditions for extended periods of time may affect product reliability.

Thermal Impedance

Parameter Symbol

Conditions SOURCE = 0 V; TJ = -40 to 125 °C

See Figure 54 (Unless Otherwise Specified)

Min Typ Max Units

Control Functions

Switching Frequency in Full Frequency Mode (average)

fOSC TJ = 25 °C

FREQUENCY PinConnected to SOURCE

119 132 145

kHz

TOP252-258Y TOP255-262L TOP252-262E

FREQUENCY PinConnected to CONTROL

59.4 66 72.6TOP252-258Y TOP255-262L TOP252-262E

TOP252-258P/G/M TOP259-261Y 59.4 66 72.6

Frequency Jitter Deviation

Df132 kHz Operation ±5

kHz66 kHz Operation ±2.5

Frequency Jitter Modulation Rate

fM 250 Hz

Maximum Duty Cycle DCMAX IC = ICD1

IV ≤ IV(DC) or IM ≤ IM(DC) or

VV, VM = 0 V75 78 83

%

IV or IM = 95 mA 30

Soft-Start Time tSOFT TJ = 25 °C 17 ms

PWM Gain DCreg TJ = 25 °CTOP252-255 -31 -25 -20

%/mATOP256-258 -27 -22 -17TOP259-262 -25 -20 -15

PWM Gain Temperature Drift

See Note A -0.01 %/mA/°C

External Bias Current IB 66 kHz OperationTOP252-255 0.9 1.5 2.1

mATOP256-258 1.0 1.6 2.2TOP259-262 1.1 1.7 2.4

Thermal Impedance: Y Package: (qJA) ........................................... 80 °C/W(1)

(qJC) ............................................. 2 °C/W(2)

P, G and M Packages: (qJA) ......................... .70 °C/W(3); 60 °C/W(4)

(qJC) .......................................... .11 °C/W(5)

E/L Package: (qJA) ............................................105 °C/W(1)

(qJC) ............................................. 2 °C/W(2)

Notes: 1. Free standing with no heat sink. 2. Measured at the back surface of tab. 3. Soldered to 0.36 sq. in. (232 mm2), 2 oz. (610 g/m2) copper clad. 4. Soldered to 1 sq. in. (645 mm2), 2 oz. (610 g/m2) copper clad.5. Measured on the SOURCE pin close to plastic interface.

Rev. H 06/13

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TOP252-262

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Parameter SymbolConditions

SOURCE = 0 V; TJ = -40 to 125 °C (Unless Otherwise Specified)

Min Typ Max Units

Control Functions (cont.)

External Bias Current IB 132 kHz Operation

TOP252-255 1.0 1.6 2.2

mATOP256-258 1.3 1.9 2.5

TOP259-262 1.6 2.2 2.9

CONTROL Current at 0% Duty Cycle

IC(OFF)

66 kHz Operation

TOP252-255 4.4 5.8

mA

TOP256-258 4.7 6.1

TOP259-262 5.1 6.5

132 kHz Operation

TOP252-255 4.6 6.0

TOP256-258 5.1 6.5

TOP259-262 6.0 7.4

Dynamic Impedance ZC IC = 4 mA; TJ = 25 °C, See Figure 52 10 18 22 W

Dynamic Impedance Temperature Drift

0.18 %/°C

CONTROL Pin Internal Filter Pole

7 kHz

Upper Peak Current to Set Current Limit Ratio

kPS(UPPER)

TJ = 25 °C See Note B

50 55 60 %

Lower Peak Current to Set Current Limit Ratio

kPS(LOWER)

TJ = 25 °CSee Note B

25 %

Multi-Cycle- Modulation Switching Frequency

fMCM(MIN) TJ = 25 °C 30 kHz

Minimum Multi-Cycle-Modulation On Period

TMCM(MIN) TJ = 25 °C 135 ms

Shutdown/Auto-Restart

Control Pin Charging Current

IC(CH) TJ = 25 °CVC = 0 V -5.0 -3.5 -1.0

mAVC = 5 V -3.0 -1.8 -0.6

Charging Current Temperature Drift

See Note A 0.5 %/°C

Auto-Restart Upper Threshold Voltage

VC(AR)U 5.8 V

Auto-Restart Lower Threshold Voltage

VC(AR)L 4.5 4.8 5.1 V

Multi-Function (M), Voltage Monitor (V) and External Current Limit (X) Inputs

Auto-Restart Hysteresis Voltage

VC(AR)hyst 0.8 1.0 V

Auto-Restart Duty Cycle

DC(AR) 2 4 %

Auto-Restart Frequency

f(AR) 0.5 Hz

Line Undervoltage Threshold Current and Hysteresis (M or V Pin)

IUV TJ = 25 °CThreshold 22 25 27 mA

Hysteresis 14 mA

Line Overvoltage Threshold Current and Hysteresis (M or V Pin)

IOV TJ = 25 °CThreshold 107 112 117 mA

Hysteresis 4 mA

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TOP252-262

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Min Typ Max Units

Multi-Function (M), Voltage Monitor (V) and External Current Limit (X) Inputs

Output Overvoltage Latching Shutdown Threshold Current

IOV(LS) TJ = 25 °C 269 336 403 mA

V or M Pin Reset Voltage VV(TH) or VM(TH)

TJ = 25 °C 0.8 1.0 1.6 V

Remote ON/OFF Negative Threshold Current and Hysteresis (M or X Pin)

IREM (N) TJ = 25 °CThreshold -35 -27 -20

mAHysteresis 5

V or M Pin Short Circuit Current

IV(SC) or

IM(SC)

TJ = 25 °C VV, VM = VC 300 400 500 mA

X or M Pin Short Circuit Current

IX(SC) or

IM(SC)

VX, VM = 0 VNormal Mode -260 -200 -140

mAAuto-Restart Mode -95 -75 -55

V or M Pin Voltage (Positive Current)

VV or VM

IV or IM = IUV 2.10 2.8 3.20

VIV or IM = IOV

TOP252-TOP257 2.79 3.0 3.21

TOP258-TOP262 2.83 3.0 3.25

V or M Pin Voltage Hysteresis (Positive Current)

VV(hyst) or VM(hyst)

IV or IM = IOV 0.2 0.5 V

X or M Pin Voltage (Negative Current)

VX or VM

IX or IM = -50 mA 1.23 1.30 1.37V

IX or IM = -150 mA 1.15 1.22 1.29

Maximum Duty Cycle Reduction Onset Threshold Current

IV(DC) or

IM(DC)

IC ≥ IB, TJ = 25 °C 18.9 22.0 24.2 mA

Maximum Duty Cycle Reduction Slope

TJ = 25 °C

IV(DC) < IV <48 mA or IM(DC) < IM <48 mA

-1.0

%/mA

IV or IM ≥48 mA -0.25

Remote OFF DRAIN Supply Current

ID(RMT) VDRAIN = 150 V

X, V or M Pin Floating

0.6 1.0mA

V or M Pin Shorted to CONTROL

1.0 1.6

Remote ON Delay tR(ON)

From Remote ON to Drain Turn-On

See Note B

66 kHz 3.0ms

132 kHz 1.5

Remote OFF Setup Time

tR(OFF)

Minimum Time Before Drain Turn-On to Disable Cycle

See Note B

66 kHz 3.0ms

132 kHz 1.5

Frequency Input

FREQUENCY Pin Threshold Voltage

VF See Note B 2.9 V

FREQUENCY Pin Input Current

IF TJ = 25 °C VF = VC 10 55 90 mA

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TOP252-262

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Min Typ Max Units

Circuit Protection

Self Protection Current Limit(See Note C)

ILIMIT

TOP252PN/GN/MN TJ = 25 °C

di/dt = 45 mA/ms 0.400 0.43 0.460

A

TOP252EN TJ = 25 °C

di/dt = 90 mA/ms 0.400 0.43 0.460

TOP253PN/GN TJ = 25 °C

di/dt = 80 mA/ms 0.697 0.75 0.803

TOP253MN TJ = 25 °C

di/dt = 90 mA/ms 0.790 0.85 0.910

TOP253EN TJ = 25 °C

di/dt = 180 mA/ms 0.790 0.85 0.910


di/dt = 105 mA/ms 0.93 1.00 1.07


di/dt = 135 mA/ms 1.209 1.30 1.391

TOP254YN/EN TJ = 25 °C

di/dt = 270 mA/ms 1.209 1.30 1.391


di/dt = 120 mA/ms 1.069 1.15 1.231


di/dt = 175 mA/ms 1.581 1.70 1.819

TOP255LN TJ = 25 °C

di/dt = 350 mA/ms 1.581 1.70 1.819


di/dt = 350 mA/ms 1.581 1.70 1.819


di/dt = 140 mA/ms 1.255 1.35 1.445


di/dt = 220 mA/ms 1.953 2.10 2.247


di/dt = 435 mA/ms 1.953 2.10 2.247


di/dt = 530 mA/ms 2.371 2.55 2.729


di/dt = 155 mA/ms 1.395 1.50 1.605


di/dt = 265 mA/ms 2.371 2.55 2.729


di/dt = 530 mA/ms 2.371 2.55 2.729


di/dt = 705 mA/ms 3.162 3.40 3.638


di/dt = 170 mA/ms 1.534 1.65 1.766


di/dt = 310 mA/ms 2.790 3.00 3.210


di/dt = 620 mA/ms 2.790 3.00 3.210

Rev. H 06/13

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TOP252-262

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Min Typ Max Units

Circuit Protection (cont.)

Self Protection Current Limit(See Note C)

ILIMIT

TOP258YN/EN TJ = 25 °C di/dt = 890 mA/ms 3.999 4.30 4.601

A

TOP259LN TJ = 25 °C di/dt = 720 mA/ms 3.236 3.48 3.724







TOP262EN TJ = 25 °C di/dt = 1530 mA/ms 6.882 7.40 7.918

Initial Current Limit IINIT See Note B 0.70 × ILIMIT(MIN)

A

Power Coefficient PCOEFF

TJ = 25 °C, See Note D

IX or IM ≤ - 165 mA 0.9 × I2f I2f 1.2 × I2fA2kHz

IX or IM ≤ - 117 mA 0.9 × I2f I2f 1.2 × I2f

Leading Edge Blanking Time

tLEB TJ = 25 °C, See Figure 53 220 ns

Current Limit Delay tIL(D) 100 ns

Thermal Shutdown Temperature

135 142 150 °C

Thermal Shutdown Hysteresis

75 °C

Power-Up Reset Threshold Voltage

VC(RESET) Figure 54 (S1 Open Condition) 1.75 3.0 4.25 V

Output

ON-State Resistance

RDS(ON)

TOP252 ID = 50 mA

TJ = 25 °C 19.1 22.00

W

TJ = 100 °C 28.8 33.40

TOP253 ID = 100 mA

TJ = 25 °C 8.8 10.10

TJ = 100 °C 13.1 15.20

TOP254 ID = 150 mA

TJ = 25 °C 5.4 6.25

TJ = 100 °C 8.35 9.70

TOP255 ID = 200 mA

TJ = 25 °C 4.1 4.70

TJ = 100 °C 6.3 7.30

TOP256 ID = 300 mA

TJ = 25 °C 2.8 3.20

TJ = 100 °C 4.1 4.75

TOP257 ID = 400 mA

TJ = 25 °C 2.0 2.30

TJ = 100 °C 3.1 3.60

TOP258 ID = 500 mA

TJ = 25 °C 1.7 1.95

TJ = 100 °C 2.5 2.90

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TOP252-262

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NOTES:A. For specifications with negative values, a negative temperature coefficient corresponds to an increase in magnitude with increas-

ing temperature, and a positive temperature coefficient corresponds to a decrease in magnitude with increasing temperature.

B. Guaranteed by characterization. Not tested in production.

C. For externally adjusted current limit values, please refer to Figures 55a and 55b (Current Limit vs. External Current Limit Resis-tance) in the Typical Performance Characteristics section. The tolerance specified is only valid at full current limit.

D. I2f calculation is based on typical values of ILIMIT and fOSC, i.e. ILIMIT(TYP)2 × fOSC, where fOSC = 66 kHz or 132 kHz depending on package

/ F pin connection. See fOSC specification for detail.

E. The TOPSwitch-HX will start up at 18 VDC drain voltage. The capacitance of electrolytic capacitors drops significantly at tempera-tures below 0 °C. For reliable start up at 18 V in sub zero temperatures, designers must ensure that circuit capacitors meet recommended capacitance values.

F. Breakdown voltage may be checked against minimum BVDSS specification by ramping the DRAIN pin voltage up to but not exceeding minimum BVDSS.



Min Typ Max Units

Output (cont.)

ON-State Resistance

RDS(ON)

TOP259 ID = 600 mA

TJ = 25 °C 1.45 1.70

W

TJ = 100 °C 2.25 2.60

TOP260 ID = 700 mA

TJ = 25 °C 1.20 1.40

TJ = 100 °C 1.80 2.10

TOP261 ID = 800 mA

TJ = 25 °C 1.05 1.20

TJ = 100 °C 1.55 1.80

TOP262 ID = 900 mA

TJ = 25 °C 0.90 1.05

TJ = 100 °C 1.35 1.55

DRAIN Supply VoltageTJ ≤ 85 °C, See Note E 18

V36

OFF-State Drain Leakage Current

IDSS

VV, VM = Floating, IC = 4 mA, VDS = 560 V, TJ = 125 °C

470 mA

Breakdown Voltage

BVDSS

VV, VM = Floating, IC = 4 mA, TJ = 25 °C See Note F

700 V

Rise Time tR Measured in a Typical FlybackConverter Application

100 ns

Fall Time tF 50 ns

Supply Voltage Characteristics

Control Supply/ Discharge Current

ICD1

Output MOSFET Enabled

VX, VV, VM = 0 V

66 kHz Operation

TOP252-255 0.6 1.2 2.0

mA

TOP256-258 0.9 1.4 2.3

TOP259-262 1.1 1.6 2.5

132 kHz Operation

TOP252-255 0.8 1.3 2.2

TOP256-258 1.1 1.6 2.5

TOP259-262 1.5 2.2 2.9

ICD2

Output MOSFET Disabled VX, VV, VM = 0 V

0.3 0.6 1.3

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Figure 51. Duty Cycle Measurement.

Figure 52. CONTROL Pin I-V Characteristic. Figure 53. Drain Current Operating Envelope.

Figure 54. TOPSwitch-HX General Test Circuit.

PI-2039-033001

DRAINVOLTAGE

HV

0 V

90%

10%

90%

t2

t1

D = t1t2

120

100

80

40

20

60

05 6 7 8 9

CONTROL Pin Voltage (V)

CO

NT

RO

L P

in C

urr

ent

(mA

)

1Slope

DynamicImpedance

=

PI-

4737

-061

207

0.8

1.31.21.1

0.90.8

1.0

00 1 2 6 83

Time (µs)

DR

AIN

Cu

rren

t (n

orm

aliz

ed)

PI-

4758

-061

407

4 5 7

0.70.60.50.40.30.20.1

IINIT(MIN)

tLEB (Blanking Time)

PI-4738-071408

5-50 V

5-50 V

S4

40 V

0.1 µF47 µF

470 Ω5 W

TOP254-258 Y, all E, L or M Packages (X and V Pins)

P or G Package (M Pin)

470 Ω

0-300 kΩ

0-60 kΩ

0-60 kΩ

0-300 kΩ

NOTES: 1. This test circuit is not applicable for current limit or output characteristic measurements. 2. For P, G and M packages, short all SOURCE pins together.

D

DSF X

C

V

M

CCONTROL

TOPSwitch-HX

S1 S5

S30-15 V

S2

SG X

CCONTROL

TOP259-261 Y (X and V Pins)

5-50 V

0-300 kΩ

Rev. H 06/13

39

TOP252-262

www.powerint.com

Figure 55a. Normalized Current Limit vs. X or M Pin Current.

Figure 55b. Normalized Current Limit vs. External Current Limit Resistance.

PI-4754-120307

0

0.1

0.2

0.3

0.4

0.5

0.6

0.7

0.8

0.9

1

1.1

-200 -150 -100 -50 0

IX or IM ( µA )

0

0.1

0.2

0.3

0.4

0.5

0.6

0.7

0.8

0.9

1

1.1

Typical

Notes:1. Maximum and Minimum levels are based on characterization.

2. T J = 0 OC to 125 OC.

Minimum

Maximum

Nor

mal

ized

Cur

rent

Lim

it

Nor

mal

ized

di/d

t

PI-4755-120307

0

0.1

0.2

0.3

0.4

0.5

0.6

0.7

0.8

0.9

1

1.1

0 5 10 15 20 25 30 35 40 45

RIL ( kΩ )

0

0.1

0.2

0.3

0.4

0.5

0.6

0.7

0.8

0.9

1

1.1Notes:1. Maximum and Minimum levels are based on characterization.

2. T J = 0 OC to 125 OC.3. Includes the variation of X or M pin voltage

Typical

Maximum

Minimum

Norm

aliz

ed C

urre

nt L

imit

Norm

aliz

ed d

i/dt

.

Typical Performance Characteristics

Rev. H 06/13

40

TOP252-262

www.powerint.com

Typical Performance Characteristics (cont.)

1.1

1.0

0.9-50 -25 0 25 50 75 100 125 150

Junction Temperature (°C)

Bre

akd

ow

n V

olt

age

(No

rmal

ized

to

25

°C) PI-

176B

-033

001 1.2

1.0

0.8

0.6

0.4

0.2

0-50 -25 0 25 50 75 100 125 150


PI-

4759

-061

407

Ou

tpu

t F

req

uen

cy(N

orm

aliz

ed t

o 2

5 °C

)

1.2

1.0

0.8

0.6

0.4

0.2

0-50 -25 0 25 50 75 100 125 150


PI-

4760

-061

407

Cu

rren

t L

imit

(No

rmal

ized

to

25

°C)

1.2

1.0

0.8

0.6

0.4

0.2

0-50 -25 0 25 50 75 100 125 150

Junction Temperature (ϒC)

PI-4

739-

0615

07

Curr

ent L

imit

(Nor

mal

ized

to 2

5 ϒC

)

1.2

1.0

0.8

0.6

0.4

0.2

0-50 -25 0 25 50 75 100 125 150


PI-

4761

-061

407

Ove

rvo

ltag

e T

hre

sho

ld(N

orm

aliz

ed t

o 2

5 °C

)

1.2

1.0

0.8

0.6

0.4

0.2

0-50 -25 0 25 50 75 100 125 150


PI-

4762

-061

407

Un

der

-Vo

ltag

e T

hre

sho

ld(N

orm

aliz

ed t

o 2

5 °C

)

Figure 56. Breakdown Voltage vs. Temperature. Figure 57. Frequency vs. Temperature.

Figure 58. Internal Current Limit vs. Temperature. Figure 59. External Current Limit vs. Temperature with RIL = 10.5 kW.

Figure 60. Overvoltage Threshold vs. Temperature. Figure 61. Undervoltage Threshold vs. Temperature.

Rev. H 06/13

41

TOP252-262

www.powerint.com


6

4.5

5.5

5

20 100 200 500400300

VOLTAGE-MONITOR Pin Current (µA)

VO

LTA

GE

MO

NIT

OR

Pin

Vo

ltag

e (V

)

PI-

4740

-060

607

3

2.5

3.5

4

1.6

1.0

1.4

1.2

0-200 -150 -50-100 0

EXTERNAL CURRENT LIMIT Pin Current (µA)

EX

TE

RN

AL

CU

RR

EN

T L

IMIT

P

in V

olt

age

(V)

PI-

4741

-110

907

0.4

0.2

0.6

0.8

VX = 1.354 - 1147.5 × IX + 1.759 × 106 × (IX)2 with -180 µA < IX < -25 µA

6

5

4

3

2

1

0-200 -100 0 100 200 300 400 500

PI-

4742

-021

308

MU

LTI-

FU

NC

TIO

N P

in V

olt

age

(V)

MULTI-FUNCTION Pin Current (µA)

See expandedversion(Figure 63b)

1.2

1.4

1.6

0.4

0.6

0.2

0.8

1.0

0-200 -150 -50-100 0

MU

LTI-

FU

NC

TIO

N P

in V

olt

age

(V)

PI-

4743

-061

407

MULTI-FUNCTION Pin Current (µA)

VM = 1.354 - 1147.5 × IM + 1.759 × 106 × (IM)2 with -180 µA < IM < -25 µA

1.2

1.0

0.8

0.6

0.4

0.2

0-50 -25 0 25 50 75 100 125 150


PI-

4763

-072

208

CO

NT

RO

L C

urr

ent

(No

rmal

ized

to

25

°C)

1.2

1.0

0.8

0.6

0.4

0.2

0-50 -25 0 25 50 75 100 125 150


PI-

4764

-061

407

On

set

Th

resh

old

Cu

rren

t(N

orm

aliz

ed t

o 2

5 °C

)

Figure 62b. EXTERNAL CURRENT LIMIT Pin Voltage vs. Current.

Figure 63a. MULTI-FUNCTION Pin Voltage vs. Current. Figure 63b. MULTI-FUNCTION Pin Voltage vs. Current (Expanded).

Figure 64. Control Current Out at 0% Duty Cycle vs. Temperature. Figure 65. Maximum Duty Cycle Reduction Onset Threshold Current vs. Temperature.

Figure 62a. VOLTAGE-MONITOR Pin vs. Current.

Rev. H 06/13

42

TOP252-262

www.powerint.com


1

-0.5

0

0.5

-2.50 20 40 60 80 100

Drain Pin Voltage (V)

CO

NT

RO

L P

in C

urr

ent

(mA

)

PI-

4744

-072

208

-1.5

-2

-1

VC = 5 V

Figure 66. Output Characteristics. Figure 67. IC vs. DRAIN Voltage.

Figure 68. COSS vs. DRAIN Voltage. Figure 69. DRAIN Capacitance Power.

Figure 70. Remote OFF DRAIN Supply Current vs. Temperature.

5

00 2 4 6 8 10 12 14 16 18 20

Drain Voltage (V)

DR

AIN

Cu

rren

t (A

) PI-

4748

-071

708

2

1

TCASE = 25 °CTCASE = 100 °C

4

3TOP262 1.82TOP261 1.62TOP260 1.42TOP259 1,17TOP258 1.00TOP257 0.85TOP256 0.61TOP255 0.42TOP254 0.32TOP253 0.20 TOP252 0.10

Scaling Factors:

0 100 200 300 400 500 60010

100

1000

10000

PI-

4749

-071

708


DR

AIN

Cap

acit

ance

(p

F) TOP262 1.82

TOP261 1.62TOP260 1.42TOP259 1.17TOP258 1.00TOP257 0.85TOP256 0.61TOP255 0.42TOP254 0.32TOP253 0.20 TOP252 0.10

Scaling Factors:500

400

200

100

300

00 200100 400 500 600300 700


Po

wer

(m

W)

PI-

4750

-071

708

132 kHz

66 kHz

TOP262 1.82TOP261 1.62TOP260 1.42TOP259 1.17TOP258 1.00TOP257 0.85TOP256 0.61TOP255 0.42TOP254 0.32TOP253 0.20 TOP252 0.10

Scaling Factors:

1.2

0.8

1.0

0-50 0-25 5025 10075 125 150


Rem

ote

OF

F D

RA

IN S

up

ply

Cu

rren

t (

No

rmal

ized

to

25

°C)

PI-

4745

-061

407

0.2

0.4

0.6

Rev. H 06/13

43

TOP252-262

www.powerint.com

PI-2644-040110

Notes:1. Controlling dimensions are inches. Millimeter dimensions are shown in parentheses. 2. Pin numbers start with Pin 1, and continue from left to right when viewed from the front.3. Dimensions do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15 mm) on any side.4. Minimum metal to metal spacing at the package body for omitted pin locations is .068 in. (1.73 mm).5. Position of terminals to be measured at a location .25 (6.35) below the package body.6. All terminals are solder plated.

Y07C

PIN 1 PIN 7

MOUNTING HOLE PATTERN

.050 (1.27)

.150 (3.81)

.050 (1.27)

.150 (3.81)

.050 (1.27)

.050 (1.27)

.100 (2.54)

.180 (4.58).200 (5.08)

PIN 1

+

.010 (.25) M

.461 (11.71)

.495 (12.57)

.390 (9.91).420 (10.67).146 (3.71)

.156 (3.96)

.860 (21.84)

.880 (22.35)

.024 (.61)

.034 (.86)

.068 (1.73) MIN

.050 (1.27) BSC

.150 (3.81) BSC

.108 (2.74) REF

PIN 1 & 7

7° TYP.

PIN 2 & 4

.040 (1.02)

.060 (1.52)

.190 (4.83)

.210 (5.33)

.012 (.30)

.024 (.61)

.080 (2.03)

.120 (3.05)

.234 (5.94)

.261 (6.63)

.165 (4.19)

.185 (4.70)

.040 (1.02)

.060 (1.52)

.045 (1.14)

.055 (1.40)

.670 (17.02) REF.

.570 (14.48) REF.

TO-220-7C (Y Package)

Rev. H 06/13

44

TOP252-262

www.powerint.com

Notes:1. Package dimensions conform to JEDEC specification MS-001-AB (Issue B 7/85) for standard dual-in-line (DIP) package with .300 inch row spacing.2. Controlling dimensions are inches. Millimeter sizes are shown in parentheses.3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side.4. Pin locations start with Pin 1, and continue counter-clock- wise to Pin 8 when viewed from the top. The notch and/or dimple are aids in locating Pin 1. Pin 3 is omitted.5. Minimum metal to metal spacing at the package body for the omitted lead location is .137 inch (3.48 mm).6. Lead width measured at package body. 7. Lead spacing measured with the leads constrained to be perpendicular to plane T.

.008 (.20)

.015 (.38)

.300 (7.62) BSC(NOTE 7)

.300 (7.62)

.390 (9.91)

.367 (9.32)

.387 (9.83)

.240 (6.10)

.260 (6.60)

.125 (3.18)

.145 (3.68)

.057 (1.45)

.068 (1.73)

.120 (3.05)

.140 (3.56)

.015 (.38)MINIMUM

.048 (1.22)

.053 (1.35).100 (2.54) BSC

.014 (.36)

.022 (.56)

-E-

Pin 1

SEATINGPLANE

-D-

-T-

P08C

PDIP-8C (P Package)

PI-3933-040110

D S .004 (.10)⊕

T E D S .010 (.25) M⊕

(NOTE 6)

.137 (3.48)MINIMUM

Notes:1. Package dimensions conform to JEDEC specification MS-019.2. Controlling dimensions are inches. Millimeter sizes are shown in parentheses.3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side.4. D, E and F are reference datums.5. Dimensioning and tolerancing conform to ASME Y14.5M-1994.

.008 (.20)

.015 (.38)

.300 (7.62)

.390 (9.91)

.240 (6.10)

.260 (6.60)

10 6

1 5

.200 (5.08) Max

.020 (.51) Min

.367 (9.32)

.387 (9.83)

.120 (3.05)

.140 (3.56)

.030 (.76).040 (1.02)

.070 (1.78) BSC .300 BSC

.300 (7.62).340 (8.64

.014 (.36)

.022 (.56)

.125 (3.18)

.145 (3.68)

-E-

SEATINGPLANE

-D-

P10C

SDIP-10C (M Package)

PI-4648-101507

F D E.010 (.25) M⊕

-F-

Rev. H 06/13

45

TOP252-262

www.powerint.com

SMD-8C (G Package)

PI-4015-101507

.004 (.10)

.012 (.30).036 (0.91).044 (1.12)

.004 (.10)

0 - ° 8°

.367 (9.32)

.387 (9.83)

.048 (1.22).009 (.23)

.053 (1.35).032 (.81).037 (.94)

.125 (3.18)

.145 (3.68)

-D-

Notes:1. Controlling dimensions are inches. Millimeter sizes are shown in parentheses.2. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side.3. Pin locations start with Pin 1, and continue counter-clock- wise to Pin 8 when viewed from the top. Pin 3 is omitted.4. Minimum metal to metal spacing at the package body for the omitted lead location is .137 inch (3.48 mm).5. Lead width measured at package body. 6. D and E are referenced datums on the package body.

.057 (1.45)

.068 (1.73)(NOTE 5)

E S

.100 (2.54) (BSC)

.372 (9.45).240 (6.10)

.388 (9.86).260 (6.60)

.010 (.25)

-E-

Pin 1

D S .004 (.10)⊕

⊕

G08C

.420

.046 .060 .060 .046

.080

Pin 1

.086

.186

.286

Solder Pad Dimensions.137 (3.48) MINIMUM

Rev. H 06/13

46

TOP252-262

www.powerint.com

PI-4917-061510

MOUNTING HOLE PATTERN (not to scale)

PIN 7

PIN 1

0.100 (2.54) 0.100 (2.54)

0.059 (1.50)

0.059 (1.50)

0.050 (1.27)

0.050 (1.27)

0.100 (2.54)

0.155 (3.93)

0.020 (0.50)

Notes:1. Dimensioning and tolerancing per ASME Y14.5M-1994.

2. Dimensions noted are determined at the outermost extremes of the plastic body exclusive of mold flash, tie bar burrs, gate burrs, and interlead flash, but including any mismatch between the top and bottom of the plastic body. Maximum mold protrusion is 0.007 [0.18] per side.

3. Dimensions noted are inclusive of plating thickness.

4. Does not include inter-lead flash or protrusions.

5. Controlling dimensions in inches (mm).

0.403 (10.24)0.397 (10.08)

0.325 (8.25)0.320 (8.13)

0.050 (1.27)

FRONT VIEW

2

2

B

A

0.070 (1.78) Ref.

Pin #1I.D.

3

C

0.016 (0.41)Ref.

0.290 (7.37)Ref.

0.047 (1.19)

0.100 (2.54)

0.519 (13.18)Ref.

0.198 (5.04) Ref.

0.264 (6.70)Ref.

0.118 (3.00)6×6×

3

0.140 (3.56)0.120 (3.05)

0.021 (0.53)0.019 (0.48)

0.378 (9.60)Ref. 0.019 (0.48) Ref.

0.060 (1.52)Ref.

0.048 (1.22)0.046 (1.17)

0.081 (2.06)0.077 (1.96)

0.207 (5.26)0.187 (4.75)

0.033 (0.84)0.028 (0.71)0.016 (0.41)

0.011 (0.28)

eSIP-7C (E Package)

10° Ref.All Around

0.020 M 0.51 M C0.010 M 0.25 M C A B

SIDE VIEW

END VIEW

BACK VIEW

4

0.023 (0.58)

0.027 (0.70)

DETAIL A

Detail A

Rev. H 06/13

47

TOP252-262

www.powerint.com

1 7

END VIEW

0.021 (0.53)0.019 (0.48)0.060 (1.52) Ref.

0.019 (0.48) Ref. 0.378 (9.60)Ref.

0.048 (1.22)0.046 (1.17)

C

SIDE VIEW

6×

0.129 (3.28)0.122 (3.08)

0.081 (2.06)0.077 (1.96)

Detail A

0.084 (2.14)

0.047 (1.19) Ref.

0.290 (7.37)Ref.

0.016 (0.41)0.011 (0.28)

0.020 M 0.51 M C

3

PI-5204-061510

Notes:1. Dimensioning and tolerancing per ASME Y14.5M-1994. 2. Dimensions noted are determined at the outermost extremes of the plastic body exclusive of mold flash, tie bar burrs, gate burrs, and interlead flash, but including any mismatch between the top and bottom of the plastic body. Maximum mold protrusion is 0.007 [0.18] per side.3. Dimensions noted are inclusive of plating thickness.4. Does not include inter-lead flash or protrusions.5. Controlling dimensions in inches (mm).

eSIP-7F (L Package)

2

A

B

1 7

BOTTOM VIEW

Pin 1 I.D.

0.403 (10.24)0.397 (10.08)

0.325 (8.25)0.320 (8.13)

0.050 (1.27)0.070 (1.78) Ref.

Exposed pad hidden Exposed pad up

2

17

TOP VIEW

0.089 (2.26)0.079 (2.01)

0.173 (4.40)0.163 (4.15)

0.198 (5.04) Ref.

0.264 (6.70) Ref.

0.100 (2.54)

0.490 (12.45) Ref.

6×0.033 (0.84)0.028 (0.71)

0.010 M 0.25 M C A B

43

0.020 (0.50)

0.023 (0.58)

0.027 (0.70)

DETAIL A (Not drawn to scale)

Rev. H 06/13

48

TOP252-262

www.powerint.com

Part Ordering Information

• TOPSwitch Product Family

• HX Series Number

• Package Identifier

P Plastic DIP-8C

G Plastic SMD-8C

M Plastic SDIP-10C

Y Plastic TO-220-7C

E Plastic eSIP-7C

L Plastic eSIP-7F

• Pin Finish

N Pure Matte Tin (Pb-Free) (P, G, M, E, L and Y Packages)

G Green Mold Compound (Specific E Packages Only)

• Tape & Reel and Other Options

Blank Standard Configurations

TL G Package (1000 min/mult.)TOP 258 G N - TL

Rev. H 06/13

49

TOP252-262

www.powerint.com

Revision Notes DateB Data sheet release. 02/08C Added L package and TOP262. 07/08D Changed eSIP-7E to eSIP-7F. Added detail to PI-4917 and PI-5204. 08/08E Released TOP255-259LN and TOP262EN parts. 10/08F Added note for TOP256E halogen free part availability. 01/09

GAdded note for TOP258P and TOP259E halogen free part availability. Updated E & L bend package drawings. Minor text changes to page 27.

01/10

H Added EG parts. Removed Note 7 from Table 1 on page 2. 06/13

For the latest updates, visit our website: www.powerint.comPower Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power Integrations does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS MAKES NO WARRANTY HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD PARTY RIGHTS.

Patent InformationThe products and applications illustrated herein (including transformer construction and circuits external to the products) may be covered by one or more U.S. and foreign patents, or potentially by pending U.S. and foreign patent applications assigned to Power Integrations. A complete list of Power Integrations patents may be found at www.powerint.com. Power Integrations grants its customers a license under certain patent rights as set forth at http://www.powerint.com/ip.htm.

Life Support PolicyPOWER INTEGRATIONS PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF POWER INTEGRATIONS. As used herein:

1. A Life support device or system is one which, (i) is intended for surgical implant into the body, or (ii) supports or sustains life, and (iii) whose failure to perform, when properly used in accordance with instructions for use, can be reasonably expected to result in significant injury or death to the user.

2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness.

The PI logo, TOPSwitch, TinySwitch, LinkSwitch, LYTSwitch, DPA-Switch, PeakSwitch, CAPZero, SENZero, LinkZero, HiperPFS, HiperTFS, HiperLCS, Qspeed, EcoSmart, Clampless, E-Shield, Filterfuse, StakFET, PI Expert and PI FACTS are trademarks of Power Integrations, Inc. Other trademarks are property of their respective companies. ©2013, Power Integrations, Inc.

Power Integrations Worldwide Sales Support Locations

World Headquarters5245 Hellyer AvenueSan Jose, CA 95138, USA.Main: +1-408-414-9200Customer Service:Phone: +1-408-414-9665Fax: +1-408-414-9765e-mail: [email protected]

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