U211B2/ B3

Rev. A2, 14-Apr-981 (21)

Phase-Control Circuit - General Purpose Feedback

DescriptionThe integrated circuit U211B2/ B3 is designed as a phase-control circuit in bipolar technology with an internalfrequency-voltage converter. Furthermore, it has an inter-nal control amplifier which means it can be used forspeed-regulated motor applications.

It has an integrated load limitation, tacho monitoring andsoft-start functions, etc. to realize sophisticated motorcontrol systems.

Features� Internal frequency-to-voltage converter

� Externally-controlled integrated amplifier

� Overload limitation with a “fold back” characteristic

� Optimized soft-start function

� Tacho monitoring for shorted and open loop

� Automatic retriggering switchable

� Triggering pulse typ. 155 mA

� Voltage and current synchronization

� Internal supply-voltage monitoring

� Temperature reference source

� Current requirement ≤ 3 mA

Block Diagram

Controlamplifier

Load limitationspeed / timecontrolled

Voltagemonitoring

Supplyvoltage

limitation

Referencevoltage

Outputpulse

Pulse-blockingtacho

monitoring

Frequency-to-voltageconverter

= f (V12)

Phase-control unit

Soft start

11(10)

12(11) 13(12) 9(8) 8(7)

18*)

Voltage / currentdetector

Automaticretriggering

17(16) 1(1)

4(4)

5*)

95 10360

–VS

GND

+

–

–VRef

6(5)

7(6)

3(3)

2(2)

16(15)

10(9)

14(13)

15(14)

�

controlledcurrent sink

Figure 1. Block diagram (Pins in brackets refer to SO16)*) Pins 5 and 18 connected internally

Order InformationExtended Type Number Package Remarks

U211B2-B DIP18U211B3-BFP SO16

U211B3-BFPG3 SO16 Taped and reeled

U211B

2/ B3

Rev. A

2, 14-Apr-98

2 (21)

95 10361

R3220 k�

R4

470 k�

R2

–VS

3.3 nF

1 M�

GND

C122 25 V

C 11 2.2

R 12

180�

MR1

18 k�

1N4007 D 1

2 W

TIC226

R833 m�

1 W

R11

2 M�

100 k�R6C6

100 nF

10 /16V

C7 C8

220 nF

22 k� R7 C3 2.2 16 V

C5

1 nF

R5

1 k�Speed sensor

C4

220 nF

L

N

1 k�R10

R91 M�

4.7 /16V

C9

R19100 k�

C10

2.2 /16V

R31100 k�

R14

56 k�

R13

47 k�

VM =230 V ~

Controlamplifier

Load limitationspeed / timecontrolled Voltage

monitoring

Supplyvoltage

limitation

Referencevoltage

Outputpulse

Pulse blockingtacho

monitoring

Frequency-to-voltageconverter

Phase-control unit

Soft start

15

14

11

10

12 13 9 8

7

3

2

16

18

Voltage / currentdetector

Automaticretriggering

17 1

6

4

5

= f (V12)

+

– C2

Set speedvoltage

Actual speedvoltage

�F

�F

�F

�F

�F

�F

�

controlledcurrent sink

–VRef

Figure

2. Speed control, autom

atic retriggering, load limiting, soft start

U211B2/ B3

Rev. A2, 14-Apr-983 (21)

Pin Description

1

2

3

4

5

6

7

8

109

18

17

16

14

15

13

12

11

VS

Output

14842

Retr

VRP

CP

F/V

Isync

GND

VRef

OVL

Isense

Csoft

CTR/OPO

OP+

PB/TM

Vsync

CRV OP–

Figure 3. Pinning DIP18

Pin Symbol Function1 Isync Current synchronization2 GND Ground3 VS Supply voltage4 Output Trigger pulse output5 Retr Retrigger programming6 VRP Ramp current adjust7 CP Ramp voltage8 F/V Frequency-voltage converter9 CRV Charge pump10 OP– OP inverting input11 OP+ OP non-inverting input12 CTR/OPO Control input / OP output13 Csoft Soft start14 Isense Load current sensing15 OVL Over load adjust16 Vref Reference voltage17 Vsync Voltage synchronization18 PB/TM Pulse blocking /

tacho monitoring

VS

Output

VRP

CP

F/V

CRV

Isync

GND

1

2

3

4

5

6

7

8

16

15

14

13

12

11

10

9

14843

OVL

Isense

Csoft

CTR/OPO

OP+

OP–

Vsync

VRef

Figure 4. Pinning SO16

Pin Symbol Function1 Isync Current synchronization2 GND Ground3 VS Supply voltage4 Output Trigger pulse output5 VRP Ramp current adjust6 CP Ramp voltage7 F/V Frequency-voltage converter8 CRV Charge pump9 OP– OP inverting input10 OP+ OP non-inverting input11 CTR/OPO Control input / OP output12 Csoft Soft start13 Isense Load current sensing14 OVL Over load adjust15 Vref Reference voltage16 Vsync Voltage synchronization

U211B2/ B3

Rev. A2, 14-Apr-984 (21)

DescriptionMains Supply

The U211B2 is fitted with voltage limiting and cantherefore be supplied directly from the mains. The supplyvoltage between Pin 2 (+ pol/�) and Pin 3 builds upacross D1 and R1 and is smoothed by C1. The value of theseries resistance can be approximated using (seefigure 2):

R1�VM – VS

2 IS

Further information regarding the design of the mainssupply can be found in the design hints. The referencevoltage source on Pin 16 of typ. –8.9 V is derived fromthe supply voltage and is used for regulation.

Operation using an externally stabilized DC voltage is notrecommended.

If the supply cannot be taken directly from the mainsbecause the power dissipation in R1 would be too large,then the circuit shown in figure 5 should be used.

1 2 3 4 5

C1R1

24 V~

~

95 10362

Figure 5. Supply voltage for high current requirements

Phase Control

There is a general explanation in the data book “BipolarPower Control Circuits” on the common phase controlfunction. The phase angle of the trigger pulse is derivedby comparing the ramp voltage (which is mains synchro-nized by the voltage detector) with the set value on thecontrol input Pin 12. The slope of the ramp is determinedby C2 and its charging current. The charging current canbe varied using R2 on Pin 6. The maximum phase angle�max can also be adjusted using R2.

When the potential on Pin 7 reaches the nominal valuepredetermined at Pin 12, then a trigger pulse is generatedwhose width tp is determined by the value of C2 (the valueof C2 and hence the pulse width can be evaluated byassuming 8 �s/nF). At the same time, a latch is set, so thatas long as the automatic retriggering has not beenactivated, no more pulses can be generated in that halfcycle.

The current sensor on Pin 1 ensures that, for operationswith inductive loads, no pulse will be generated in a newhalf cycle as long as a current from the previous half cycleis still flowing in the opposite direction to the supplyvoltage at that instant. This makes sure that “gaps” in theload current are prevented.

The control signal on Pin 12 can be in the range 0 V to–7 V (reference point Pin 2).

If V 12 = –7 V, the phase angle is at maximum = �max i.e.,the current flow angle is a minimum. The phase angle�min is minimum when V12 = V2.

Voltage Monitoring

As the voltage is built up, uncontrolled output pulses areavoided by internal voltage surveillance. At the sametime, all of the latches in the circuit (phase control, loadlimit regulation, soft start) are reset and the soft-startcapacitor is short circuited. Used with a switchinghysteresis of 300 mV, this system guarantees definedstart-up behavior each time the supply voltage is switchedon or after short interruptions of the mains supply.

Soft-Start

As soon as the supply voltage builds up (t1), the integratedsoft-start is initiated. Figure 6 shows the behaviour of thevoltage across the soft-start capacitor and is identical withthe voltage on the phase-control input on Pin 12. Thisbehavior guarantees a gentle start-up for the motor andautomatically ensures the optimum run-up time.

U211B2/ B3

Rev. A2, 14-Apr-985 (21)

VC3

t

V12

V0

t1

ttot

t2t3

95 10272

Figure 6. Soft-start

t1 = build-up of supply voltaget2 = charging of C3 to starting voltaget1 + t2 = dead timet3 = run-up timettot = total start-up time to required speed

C3 is first charged up to the starting voltage V0 with tacurrent of typically 45 �A (t2). By then reducing thecharging current to approx. 4 �A, the slope of thecharging function is substantially reduced so that therotational speed of the motor only slowly increases. Thecharging current then increases as the voltage across C3increases,resulting in a progressively rising chargingfunction which accelerates the motor more and morestrongly with increasing rotational speed. The chargingfunction determines the acceleration up to the set-point.The charging current can have a maximum value of55 �A.

Frequency-to-Voltage Converter

The internal frequency-to-voltage converter (f/V-converter) generates a DC signal on Pin 10 which isproportional to the rotational speed using an AC signalfrom a tacho generator or a light beam whose frequencyis in turn dependent on the rotational speed. The high-impedance input Pin 8, compares the tacho voltage to aswitch-on threshold of typ. –100 mV. The switch-offthreshold is given with –50 mV. The hysteresisguarantees very reliable operation even when relativelysimple tacho generators are used. The tacho frequency isgiven by:

f � n60

� p (Hz)

where: n = revolutions per minutep = number of pulses per revolution

The converter is based on the charge pumping principle.With each negative half-wave of the input signal, aquantity of charge determined by C5 is internallyamplified and then integrated by C6 at the converteroutput on Pin 10. The conversion constant is determinedby C5, its charge transfer voltage of Vch, R6 (Pin 10) andthe internally adjusted charge transfer gain.

Gi�I 10

I 9� � 8.3

k = Gi � C5 � R6 � Vch

The analog output voltage is given by

VO = k � f

The values of C5 and C6 must be such that for the highestpossible input frequency, the maximum output voltageVO does not exceed 6 V. While C5 is charging up, the Rion Pin 9 is approximately 6.7 k�. To obtain goodlinearity of the f/V converter, the time constant resultingfrom Ri and C5 should be considerably less (1/5) than thetime span of the negative half-cycle for the highestpossible input frequency. The amount of remaining rippleon the output voltage on Pin 10 is dependent on C5, C6 andthe internal charge amplification.

∆VO =Gi � Vch � C5

C6

The ripple ∆Vo can be reduced by using larger values ofC6. However, the increasing speed will then also bereduced.

The value of this capacitor should be chosen to fit theparticular control loop where it is going to be used.

Pulse Blocking

The output of pulses can be blocked using Pin 18 (standbyoperation) and the system reset via the voltage monitor ifV18 ≥ –1.25 V. After cycling through the switching pointhysteresis, the output is released when V18 ≤ –1.5 Vfollowed by a soft-start such as that after turn on.

Monitoring of the rotation can be carried out byconnecting an RC network to Pin 18. In the event of ashort or open circuit, the triac triggering pulses are cut offby the time delay which is determined by R and C. Thecapacitor C is discharged via an internal resistanceRi = 2 k� with each charge transfer process of the f/Vconverter. If there are no more charge transfer processes,C is charged up via R until the switch-off threshold isexceeded and the triac triggering pulses are cut off. Foroperation without trigger pulse blocking or monitoring ofthe rotation, Pins 18 and 16 must be connected together.

U211B2/ B3

Rev. A2, 14-Apr-986 (21)

C = 1 �F10 V

95 10363

18 17 16 15

1 2 3 4

R = 1 M�

Figure 7. Operation delay

Control Amplifier (Figure 2)

The integrated control amplifier with differential inputcompares the set value (Pin 11) with the instantaneousvalue on Pin 10 and generates a regulating voltage on theoutput Pin 12 (together with the external circuitry onPin 12) which always tries to hold the actual voltage at thevalue of the set voltages. The amplifier has atransmittance of typically 1000 �A/V and a bipolarcurrent source output on Pin 12 which operates withtypically ±110 �A. The amplification and frequencyresponse are determined by R7, C7, C8 and R11 (can be leftout). For open-loop operation, C4, C5, R6, R7, C7, C8 andR11 can be omitted. Pin 10 should be connected withPin 12 and Pin 8 with Pin 2. The phase angle of thetriggering pulse can be adjusted using the voltage onPin 11. An internal limitation circuit prevents the voltageon Pin 12 from becoming more negative than V16 + 1 V.

Load Limitation

The load limitation, with standard circuitry, providesabsolute protection against overloading of the motor. Thefunction of the load limiting takes account of the fact thatmotors operating at higher speeds can safely withstandlarger power dissipations than at lower speeds due to theincreased action of the cooling fan. Similarly, consider-ations have been made for short–term overloads for themotor which are, in practice, often required. Thesebehavior are not damaging and can be tolerated.

In each positive half-cycle, the circuit measures via R10the load current on Pin 14 as a potential drop across R8and produces a current proportional to the voltage onPin 14. This current is available on Pin 15 and isintegrated by C9. If, following high-current amplitudes ora large phase angle for current flow, the voltage on C9

exceeds an internally set threshold of approximately7.3 V (reference voltage Pin 16), a latch is set and the loadlimiting is turned on. A current source (sink) controlledby the control voltage on Pin 15 now draws current fromPin 12 and lowers the control voltage on Pin 12 so that thephase angle � is increased to �max.

The simultaneous reduction of the phase angle duringwhich current flows causes firstly: a reduction of therotational speed of the motor which can even drop to zeroif the angular momentum of the motor is excessivelylarge, and secondly: a reduction of the potential on C9which in turn reduces the influence of the current sink onPin 12. The control voltage can then increase again andbring down the phase angle. This cycle of action sets upa “balanced condition” between the “current integral” onPin 15 and the control voltage on Pin 12.

Apart from the amplitude of the load current and the timeduring which current flows, the potential on Pin 12 andhence the rotational speed also affects the function of theload limiting. A current proportional to the potential onPin 10 gives rise to a voltage drop across R10, via Pin 14,so that the current measured on Pin 14 is smaller than theactual current through R8.

This means that higher rotational speeds and highercurrent amplitudes lead to the same current integral.Therefore, at higher speeds, the power dissipation mustbe greater than that at lower speeds before the internalthreshold voltage on Pin 15 is exceeded. The effect ofspeed on the maximum power is determined by theresistor R10 and can therefore be adjusted to suit eachindividual application.

If, after the load limiting has been turned on, themomentum of the load sinks below the “o-momentum”set using R10, then V15 will be reduced. V12 can then in-crease again so that the phase angle is reduced. A smallerphase angel corresponds to a larger momentum of the mo-tor and hence the motor runs up - as long as this is allowedby the load momentum. For an already rotating machine,the effect of rotation on the measured “current integral”ensures that the power dissipation is able to increase withthe rotational speed. The result is a current-controlledaccelleration run-up which ends in a small peak of accel-leraton when the set point is reached. The latch of the loadlimiting is simultaneously reset. The speed of the motoris then again under control and is capable of carrying itsfull load. The above mentioned peak of accelerationdepends upon the ripple of actual speed voltage. A largeamount of ripple also leads to a large peak of acceleration.

The measuring resistor R8 should have a value whichensures that the amplitude of the voltage across it does notexceed 600 mV.

U211B2/ B3

Rev. A2, 14-Apr-987 (21)

Design HintsPractical trials are normally needed for the exactdetermination of the values of the relevant components inthe load limiting. To make this evaluation easier, the

following table shows the effect of the circuitry on theimportant parameters of the load limiting and summa-rizes the general tendencies.

Parameters Component

R10 Increasing R9 Increasing C9 Increasing

Pmax increases decreases n.e.

Pmin increases decreases n.e.

Pmax / min increases n.e. n.e.

td n.e. decreases increases

tr n.e. increases increases

Pmax – maximum continuous power dissipation P1 = f(n) n � 0Pmin – power dissipation with no rotation P1 = f(n) n = 0td – operation delay timetr – recovery timen.e – no effect

Pulse Output Stage

The pulse output stage is short-circuit protected and cantypically deliver currents of 125 mA. For the design ofsmaller triggering currents, the function IGT = f(RGT) hasbeen given in the data sheets in figure 18.

Automatic Retriggering

The variable automatic retriggering prevents half-cycleswithout current flow, even if the triac is turned off earlier,e.g., due to a collector which is not exactly centered(brush lifter) or in the event of unsuccessful triggering. Ifnecessary, another triggering pulse is generated after atime lapse which is determined by the repetition rate setby resistance between Pin 5 and Pin 3 (R5-3). With themaximum repetition rate (Pin 5 directly connected toPin 3), the next attempt to trigger comes after a pause of4.5 tp and this is repeated until either the triac fires or thehalf-cycle finishes. If Pin 5 is connected, then only onetrigger pulse per half-cycle is generated. Because thevalue of R5-3 determines the charging current of C2, anyrepetition rate set using R5-3 is only valid for a fixed valueof C2.

General Hints and Explanation of TermsTo ensure safe and trouble-free operation, the followingpoints should be taken into consideration when circuitsare being constructed or in the design of printed circuitboards.

– The connecting lines from C2 to Pin 7 and Pin 2should be as short as possible. The connection to Pin 2should not carry any additional high current such asthe load current. When selecting C2, a lowtemperature coefficient is desirable.

– The common (earth) connections of the set-pointgenerator, the tacho generator and the finalinterference suppression capacitor C4 of the f/Vconverter should not carry load current.

– The tacho generator should be mounted withoutinfluence by strong stray fields from the motor.

– The connections from R10 and C5 should be as shortas possible.

To achieve a high noise immunity, a maximum rampvoltage of 6 V should be used.

The typical resistance R� can be calculated from I� asfollows:

R� (k�) �T(ms)� 1.13(V) � 103

C�nF) � 6(V)

T = Period duration for mains frequency(10 ms at 50 Hz)

C� = Ramp capacitor, max. ramp voltage 6 Vand constant voltage drop at R� = 1.13 V.

A 10% lower value of R� (under worst case conditions)is recommended.

U211B2/ B3

Rev. A2, 14-Apr-988 (21)

95 10716V

VGT

VL

IL

�/2 � 3/2� 2�

tp tpp = 4.5 tp

MainsSupply

TriggerPulse

LoadVoltage

LoadCurrent

�

�

Figure 8. Explanation of terms in phase relationship

Design Calculations for Mains Supply

The following equations can be used for the evaluation of the series resistor R1 for worst case conditions:

R1max� 0.85VMmin – VSmax

2 ItotR1min�

VM – VSmin

2 ISmax

P(R1max)�(VMmax – VSmin)2

2 R1

where:

VM = Mains voltageVS = Supply voltage on Pin 3Itot = Total DC current requirement of the circuit

= IS + Ip + IxISmax = Current requirement of the IC in mAIp = Average current requirement of the triggering pulseIx = Current requirement of other peripheral componentsR1 can be easily evaluated from the figures 22 to 24.

U211B2/ B3

Rev. A2, 14-Apr-989 (21)

Absolute Maximum Ratings

Reference point Pin 2, unless otherwise specified

Parameters Symbol Value UnitCurrent requirement Pin 3 –IS 30 mA

t ≤ 10 �s –is 100 mA

Synchronization current Pin 1Pin 17

t � 10 �s Pin 1t � 10 �s Pin 17

IsyncIIsyncV

±iI±iI

553535

mAmAmAmA

f/V converter Pin 8Input current II 3 mA

t � 10 �s ±iI 13 mA

Load limiting Pin 14Limiting current, negative half-wave II 5 mA

t � 10 �s 35 mA

Input voltage Pin 14Pin 15

±Vi–VI

1 V16 to 0

VV

Phase controlInput voltage Pin 12 –VI 0 to 7 VInput current Pin 12

Pin 6±II–II

5001

�AmA

Soft-startInput voltage Pin 13 –VI V16 to 0 VPulse outputReverse voltage Pin 4 VR VS to 5 VPulse blockingInput voltage Pin 18 –VI V16 to 0 VAmplifierInput voltage Pin 11Pin 9 open Pin 10

VI–VI

0 to VS V16 to 0

VV

Reference voltage sourceOutput current Pin 16 Io 7.5 mAStorage temperature range Tstg –40 to +125 °CJunction temperature Tj 125 °CAmbient temperature range Tamb –10 to +100 °C

Thermal Resistance

Parameters Symbol Maximum UnitJunction ambient DIP18

SO16 on p.c.SO16 on ceramic

RthJA

120180100

K/WK/WK/W

U211B2/ B3

Rev. A2, 14-Apr-9810 (21)

Electrical Characteristics

–VS = 13.0 V, Tamb = 25°C, reference point Pin 2, unless otherwise specified

Parameters Test Conditions / Pins Symbol Min. Typ. Max. UnitSupply voltage for mainsoperation

Pin 3 –VS 13.0 VLimit V

Supply voltage limitation –IS = 4 mA Pin 3–IS = 30 mA

–VS–VS

14.614.7

16.616.8

VV

DC current requirement –VS = 13.0 V Pin 3 IS 1.2 2.5 3.0 mAReference voltage source –IL = 10 �A Pin 16

–IL = 5 mA–VRef 8.6

8.38.9 9.2

9.1VV

Temperature coefficient Pin 16 –TCVRef 0.5 mV/KVoltage monitoringTurn-on threshold Pin 3 –VSON 11.2 13.0 VTurn-off threshold Pin 3 –VSOFF 9.9 10.9 VPhase-control currentsSynchronization current Pin 1 �IsyncI 0.35 2.0 mA

Pin 17 �IsyncV 0.35 2.0 mA

Voltage limitation �IL = 5 mA Pins 1 and 17 �VI 1.4 1.6 1.8 V

Reference ramp, see figure 9Charge current I7 = f (R6);

R6 = 50 k to 1 M� Pin 7 I7 1 20 �AR�-reference voltage � ≥ ���°C Pins 6 and 3 V�Ref 1.06 1.13 1.18 VTemperature coefficient Pin 6 TCV�Ref 0.5 mV/KPulse output, see figure 20 Pin 4Output pulse current RGT = 0, VGT = 1.2 V Io 100 155 190 mAReverse current Ior 0.01 3.0 �AOutput pulse width Cϕ = 10 nF tp 80 �sAmplifierCommon-mode signal range Pins 10 and 11 V10, 11 V16 –1 VInput bias current Pin 11 IIO 0.01 1 �AInput offset voltage Pins 10 and 11 V10 10 mVOutput current Pin 12 –IO

+IO7588

110120

145165

�A�A

Short circuit forward,transmittance

See figure 16I12 = f(V10 -11) Pin 12 Yf 1000 �A/V

Pulse blocking, tacho monitoring Pin 18Logic-on –VTON 3.7 1.5 VLogic-off –VTOFF 1.25 1.0 VInput current V18 = VTOFF = 1.25 V

V18 = V16

II14.5

0.3 1 �A�A

Output resistance RO 1.5 6 10 k�

U211B2/ B3

Rev. A2, 14-Apr-9811 (21)

UnitMax.Typ.Min.SymbolTest Conditions / PinsParametersFrequency-to-voltage converter Pin 8Input bias current IIB 0.6 2 �AInput voltage limitation See figure 15

II = –1 mAII = +1 mA

–VI+VI

6607.25

7508.05

mVV

Turn-on threshold –VTON 100 150 mVTurn-off threshold –VTOFF 20 50 mVCharge amplifierDischarge current See figure 2, C5 = 1 nF,

Pin 9Idis 0.5 mA

Charge transfer voltage Pins 9 to 16 Vch 6.50 6.70 6.90 VCharge transfer gain I10/I9 Pins 9 and 10 Gi 7.5 8.3 9.0Conversion factor See figure 2

C5 = 1 nF, R6 = 100 k� K 5.5 mV/HzOutput operating range Pins 10 to 16 VO 0-6 VLinearity �1 %Soft-start, see figures 10, 11, 12, 13, 14 f/v-converter non-activeStarting current V13 = V16, V8 = V2 Pin 13 IO 20 45 55 �AFinal current V13 = 0.5 Pin 13 IO 50 85 130 �Af/v-converter activeStarting current V13 = V16 Pin 13 IO 2 4 7 �AFinal current V13 = 0.5 IO 30 55 80 �ADischarge current Restart pulse Pin 13 IO 0.5 3 10 mAAutomatic retriggering, see figure 21 Pin 5Repetition rate R5-3 = 0 tpp 3 4.5 6 tpp

R5-3 = 15 k� tpp 20 tpLoad limiting, see figures 17, 18, 19 Pin 14Operating voltage range Pin 14 VI –1.0 1.0 VOffset current V10 = V16 Pin 14

V14 = V2 via 1 k� Pin 15–16

IO 5

0.1

12

1.0�A

Input current V10 = 4.5 V Pin 14 II 60 90 120�A

Output current V14 = 300 mV Pin 15–16 IO 110 140�A

Overload ON Pin 15–16 VTON 7.05 7.4 7.7 V

U211B2/ B3

Rev. A2, 14-Apr-9812 (21)

0 0.2 0.4 0.6 0.80

80

120

160

200

240

Pha

se A

ngle

(

)

R� ( M� )

1.0

95 10302

�° 10nF 4.7nF

Phase ControlReference Point Pin 2

2.2nF

C /t=1.5nF�

Figure 9.

0 2 4 6 80

20

40

60

80

100

I

( A

)13

V13 ( V )

10

95 10303

�

Soft Start

f/V-Converter Non ActiveReference Point Pin 16

Figure 10.

0 2 4 6 80

20

40

60

80

100

I

( A

)13

V13 ( V )

10

95 10304

�

Soft Start

f/V-Converter ActiveReference Point Pin 16

Figure 11.

0

2

4

6

8

10

V

( V

)13

t=f(C3)95 10305

Soft Start

f/V-Converter Non ActiveReference Point Pin 16

Figure 12.

0

2

4

6

8

10V

(

V )

13

t=f(C3)95 10306

Soft Start

f/V-Converter ActiveReference Point Pin 16

Figure 13.

0

2

4

6

8

10

V

( V

)13

t=f(C3)

95 10307

Soft Start

Reference Point Pin 16

Motor in ActionMotor Standstill ( Dead Time )

Figure 14.

U211B2/ B3

Rev. A2, 14-Apr-9813 (21)

–10 –8 –6 –4 –2–500

–250

0

250

500I

(

A )

8

V8 ( V )

4

95 10308

0 2

�

Reference Point Pin 2

f/V–Converter

Figure 15.

–300 –200 –100 0 200

–100

–50

0

50

100

I

( A

)12

V10–11 ( V )

300

95 10309

�

100

Control Amplifier

Reference Point for I12 = –4V

Figure 16.

0 2 4 60

50

100

150

200

–I

(

A)

12–1

6

V15–16 ( V )

8

95 10310

�

Load Limit Control

Figure 17.

0 2 4 60

50

100

150

200

I

(

A)

14–2

V10–16 (V)

8

95 10311

�

Load Limit Control

Figure 18.

0 100 200 300 4000

50

100

150

200

250

700

95 10312

500 600

I

(

A

)

15–1

6

V14–2 ( mV )

�

I15=f ( VShunt )V10=V16

Load current detection

Figure 19.

0 200 400 600 8000

20

40

60

80

100

I

( m

A )

GT

RGT ( � )

1000

95 10313

Pulse Output

VGT=0.8V1.4V

Figure 20.

U211B2/ B3

Rev. A2, 14-Apr-9814 (21)

0 6 12 18 240

5

10

15

20

R

( k

)

5–3

tpp/tp

30

95 10314

�

Automatic Retriggering

Figure 21.

0 4 8 120

10

20

30

40

50

R

( k

)

1

I tot ( mA )

16

95 10315

�

Mains Supply

Figure 22.

0 10 20 30

R1 ( k� )

40

95 10316

Mains Supply

0

1

2

3

4

6

P

(

W )

(R1)

5

Figure 23.

0 3 6 9 120

1

2

3

4

6P

( W

)(R

1)

I tot ( mA )

15

95 10317

Mains Supply

5

Figure 24.

U211B2/ B3

Rev. A2, 14-Apr-9815 (21)

1817

1615

12

34

U21

1B2

1413

12

56

7

11 8

10 9

R3

M

R1

18 k�

D1

220

k �

470

k�

R4

1.5

W

1N40

04

180�

R12

22

25 V

C1

R8=

3 x

11

m �

R10

2.2

k �

230

V~

680

pF C5

R2

1 M�

C2

2.2

nF1

k �

R5

220

nF

C4

Spe

ed s

enso

r

R7

15 k�

C7

R13

47 k�

1 M�

R11

C6

100

nF

R6

100

k �22

0 nF

C8

2.2

10 V

C3

2.2

10 V

C10

250

k �R31

4.7

10 V

C9

470

k�R

9

95 1

0364

GN

D–V

S

1 W

R15

47 k�

R16

47 k�

10 k�

R14

BZ

X55

Set

spe

edvo

ltage

L N

T1

T2

2.2

/10

V

R

C/t

�F

�F

�F

�F

�F

�

�

C11

2.2 �

F

Figure 25. Speed control, automatic retriggering, load switch-off, soft-start

The switch-off level at maximum load shows in principlethe same speed dependency as the original version (seefigure 2), but when reaching the maximum load, themotor is switched off completely.

This function is effected by the thyristor (formed by T1and T2) which ignites when the voltage at Pin 15 reachestyp. 7.4 V (reference point Pin 16). The circuit is therebyswitched in the “stand-by mode” over the release Pin 18.

U211B2/ B3

Rev. A2, 14-Apr-9816 (21)

1817

1615

12

34

U21

1B2

1413

12

56

7

11 8

10 9

R3

M

R1

18 k�

D1

220

k�

470

k �

R4

1.5

W

1N40

04

180�

R12

22

25 V

C1

R8=

3 x

11

m�

R10

2.2

k�

230

V~

680

pF C5

R2

1 M�

C2

2.2

nF1

k �R

5

220

nF

C4

Spe

ed s

enso

r

R7

15 k�

2.2

/10

V

C7

R13

47 k�

1 M�

R11

C6

100

nF

R6

100

k �22

0 nF

C8

2.2

10 V

C3

2.2

10 V

C10

250

k�R31

4.7

10 V

470

k�R

9

GN

D–V

S

1 WR16

47 k�

R15

33 k�

10 k�

R14

BZ

X55

Set

spe

edvo

ltage

L

T1

T2

R

C/t

�F

�

�

�F

�F

�F

�F

95 1

0366

N

C9

C11

2.2 �

F

Figure 26. Speed control, automatic retriggering, load switch-off, soft-start

The maximum load regulation shows the principle in thesame speed dependency as the original version (seefigure 2). When reaching the maximum load, the controlunit is turned to �max, adjustable with R2. Then only IOflows. This function is effected by the thyristor, formedby T1 and T2 which ignites as soon as the voltage at Pin 15reaches ca. 6.8 V (reference point Pin 16). The potential

at Pin 15 is lifted and kept by R14 over the internallyoperating threshold whereby the maximum loadregulation starts and adjusts the control unit constantly to�max (IO), inspite of a reduced load current. The motorshows that the circuit is still in operation in the matter ofa quiet buzzing sound.

U211B

2/ B3

Rev. A

2, 14-Apr-98

17 (21)

18 17 16 15

1 2 3 4

U211B2

14 13 12

5 6 7

11

8

10

9

R3

M

R118 k�

D1

220 k�

C11

470 k�

R4

1.5 W

1N4004

220 �

R12

22 25 V

C1

R8 = 3 x 11 m�

R10

1 k�

230 V~

1 nF

C5

R2

1 M�

C2

2.2 nF 1 k�R5

220 nF

C4

Speed sensor

R7

22 k�

C7

R13

47 k�

1.5 M�

R11

C6100 nF

R668 k�220 nF

C8

2.2 10 V

C3

2.2 10 V

C10

250 k�

R31

4.7

C91 M�

R9

95 10365

GND –VS

1 W

Set speedvoltage

L

N

1 /10 V

1 M�

2.2 /10 V

R

C /t

�

�

� F

� F

� F

� F

� F

� F

22 nFFigure

27. Speed control, autom

atic retriggering, load limiting, soft-start, tacho control

U211B2/ B3

Rev. A2, 14-Apr-9818 (21)

1817

1615

12

34

U21

1B2

1413

12

56

7

11 8

10 9

22 n

F

R4

M

R1

18 k�

D1

220

k �

C11

470

k�

R5

1.5

W

1N40

04

100 �

R6

47

25 V

C1

230

V~

680

pF

C6

R2

1 M�

C2

3.3

nF

C8

R7

470

k �

220

nF

C4

2.2

10 V

C3

4.7

10 V

C13 10

0 k �R31

95 1

0687

GN

D–V

S

10

10 V

R

C/t

R11

C7

16 k�

470

nF

Set

spe

edm

in

R18

Set

spe

edm

ax

R13

47 k�

R8

4.7

k �R3

R9

220

k�

R10

1.5

k�

100

10 V

C10

C5

470

nF

CN

Y 7

0

R17

R16

100 �

470 �

Z3

BZ

X55

C9V

13.

5 k �

/ 8

W

R15

1N40

04 D2

I GT

= 5

0 m

A

L1

L2

R14

100 �

150

nF25

0 V

~

C12

ca 2

20 P

ulse

s / R

evol

utio

n

all d

iode

s B

YW

83

�

�

�F

�F

�F

�F

�F

Figure 28. Speed control with reflective opto coupler CNY70 as emitter

U211B

2/ B3

Rev. A

2, 14-Apr-98

19 (21)

18 17 16 15

1 2 3 4

U211B2

14 13 12

5 6 7

11

8

10

9

22 nF

R3

M

R110 k�

D1

110 k�

C11

220 k�

R4

1.1 W

1N4004

100 � R12

22 25 V

C1

230 V~

C5R2

1 M�

C2

3.3 nF

C7

R11 820 k�

470 nF

C6

2.2 10 V

C3

47 10 V

C10

220 k�

R31

95 10688

GND –VS

10

RC /t

R7

C816 k�

470 nF

Set speedmin

R14

Set speedmax

R13

82 k�

R6

R5

2.2 k�

CNY 70

R17 R18

33 k� 470 �

IGT = 50 mA

100 �

150 nF250 V~

C12

680 pF

R16

10 k�

C4

1 nF

9 V

4.7 10 V

C9

R9

220 k�

R8= 3 x 0.1 �

R10

1.1 k�

C13

1

�

�

�F

�F�F

�F

�F

�F

Figure

29. Speed control, m

ax. load control with reflective opto coupler C

NY

70 as emitter

U211B2/ B3

Rev. A2, 14-Apr-9820 (21)

The circuit is designed as a speed control based on thereflection-coupled principle with 4 periods per revolutionand a max. speed of 30.000 rpm. The separation of thecoupler from the rotating aperture should be about 1 mmapproximately. In this experimental circuit, the powersupply for the coupler was provided externally because ofthe relatively high current consumption.

Instructions for adjusting:

� In the initial adjustment of the phase-control circuit,R2 should be adjusted so that when R14 = 0 and R31 arein min. position, the motor just turns.

� The speed can now be adjusted as desired by means ofR31 between the limits determined by R13 and R14.

� The switch-off power of the limiting-load control canbe set by R9. The lower R9, the higher the switch-offpower.

Package Information

13019

Package DIP18Dimensions in mm

0.5 min

technical drawingsaccording to DINspecifications

7.777.4723.3 max

4.8 max

3.36.4 max

0.36 max

9.88.2

1.641.44

0.580.48 2.54

20.32

18 10

1 9

13036

technical drawingsaccording to DINspecifications

Package SO16Dimensions in mm 10.0

9.85

8.89

0.4

1.27

1.4

0.250.10

5.24.8

3.7

3.8

6.155.85

0.2

16 9

1 8

U211B2/ B3

Rev. A2, 14-Apr-9821 (21)

Ozone Depleting Substances Policy Statement

It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to

1. Meet all present and future national and international statutory requirements.

2. Regularly and continuously improve the performance of our products, processes, distribution and operating systemswith respect to their impact on the health and safety of our employees and the public, as well as their impact onthe environment.

It is particular concern to control or eliminate releases of those substances into the atmosphere which are known asozone depleting substances (ODSs).

The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs andforbid their use within the next ten years. Various national and international initiatives are pressing for an earlier banon these substances.

TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy ofcontinuous improvements to eliminate the use of ODSs listed in the following documents.

1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively

2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the EnvironmentalProtection Agency (EPA) in the USA

3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C ( transitional substances) respectively.

TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not containsuch substances.

We reserve the right to make changes to improve technical design and may do so without further notice.Parameters can vary in different applications. All operating parameters must be validated for each customer

application by the customer. Should the buyer use TEMIC products for any unintended or unauthorizedapplication, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of,

directly or indirectly, any claim of personal damage, injury or death associated with such unintended orunauthorized use.

TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, GermanyTelephone: 49 (0)7131 67 2831, Fax number: 49 (0)7131 67 2423