mc1374
TRANSCRIPT
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Device
OperatingTemperature Range Package
M C 1 3 7 4
SEMICONDUCTOR
TECHNICAL DATA
TV MODULATOR CIRCUIT
ORDERING INFORMATION
MC1374P TA = 0 to +70C Plastic DIP
Order this document by MC1374/D
P SUFFIXPLASTIC PACKAGE
CASE 646
14
1
Figure 1. Simplified Application
+
+
+
+
+
+
+
Channel 3 4
V
S1
R1010kR1
470
L2
L1
525C7
D1MPN3404
7
6
5
4
3
2
1 14
13
12
11
10
9
8
C90.001
+VCC = 12V
Output
Video In
Audio In
L1 4 Turns #22, 1/4Dia.L2 40 Turns, #36, 3/16Dia.
4
3
VPin 11
VPin1
t
Shaded Parts Optional
C80.001
C10.001
R3470
R2470
C256
C450
C3120
C14
0.01
R62.2k
C50.001
R46.8k
R53.3k
R775 0.22H
L30.22H
L4
C150.001
C61F
C1122
C1247
C1322
U1MC1374
C1647 R1456k
R82.2k
D2
1N914
C1010F
R11220
R12180k
R1330k
R9560
1MOTOROLA ANALOG IC DEVICE DATA
T V M o d u l a t o r C i r c u i t
The MC1374 includes an FM audio modulator, sound carrier oscillator, RF
oscillator, and RF dual input modulator. It is designed to generate a TV signal
from audio and video inputs. The MC1374s wide dynamic range and low
distortion audio make it particularly well suited for applications such as video
tape recorders, video disc players, TV games and subscription decoders.
Single Supply, 5.0 V to 12 V
Channel 3 or 4 Operation
Variable Gain RF Modulator
Wide Dynamic Range
Low Intermodulation Distortion
Positive or Negative Sync
Low Audio Distortion
Few External Components
Motorola, Inc. 1996 Rev 0
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MC1374
2MOTOROLA ANALOG IC DEVICE DATA
MAXIMUM RATINGS(TA = 25C, unless otherwise noted.)
Rating Value Unit
Supply Voltage 14 Vdc
Operating Ambient Temperature Range 0 to +70 C
Storage Temperature Range 65 to +150 C
Junction Temperature 150 C
Power Dissipation Package
Derate above 25C
1.25
10 mW/C
W
ELECTRICAL CHARACTERISTICS (VCC = 12 Vdc, TA = 25C, fc = 67.25 MHz, Figure 4 circuit, unless otherwise noted.)
Characteristics Min Typ Max Unit
AM OSCILLATOR/MODULATOR
Operating Supply Voltage 5.0 12 12 V
Supply Current (Figure 1) 13 mA
Video Input Dynamic Range (Sync Amplitude) 0.25 1.0 1.0 V Pk
RF Output (Pin 9, R7 = 75 , No External Load) 170 mV pp
Carrier Suppression 36 40 dB
Linearity (75% to 12.5% Carrier, 15 kHz to 3.58 MHz) 2.0 %
Differential Gain Distortion (IRE Test Signal) 5.0 7.0 10 %
Differential Phase Distortion (3.58 MHz IRE Test Signal) 1.5 2.0 Degrees
920 kHz Beat (3.58 MHz @ 30%, 4.5 MHz @ 25%) 57 dB
Video Bandwidth (75 Input Source) 30 MHz
Oscillator Frequency Range 105 MHz
Internal Resistance across Tank (Pin 6 to Pin 7)
Internal Capacitance across Tank (Pin 6 to Pin 7)
1.8
4.0
k
pF
ELECTRICAL CHARACTERISTICS (TA = 25C, VCC = 12 Vdc, 4.5 MHz, Test circuit of Figure 11, unless otherwise noted.)
Characteristics Min Typ Max Unit
FM OSCILLATOR/MODULATORFrequency Range of Modulator
Frequency Shift versus Temperature (Pin 14 open)
Frequency Shift versus VCC (Pin 14 open)
Output Amplitude (Pin 3 not loaded)
Output Harmonics, Unmodulated
14
4.5
0.2
900
14
0.3
4.0
40
MHz
kHz/C
kHz/V
mVpp
dB
Modulation Sensitivity 1.7 MHz
4.5 MHz
10.7 MHz
0.20
0.24
0.80
MHz/V
Audio Distortion (25 kHz Deviation, Optimized Bias Pin 14)
Audio Distortion (25 kHz Deviation, Pin 14 self biased)
Incidental AM (25 kHz FM)
0.6
1.4
2.0
1.0
%
Audio Input Resistance (Pin 14 to ground)
Audio Input Capacitance (Pin 14 to ground)
6.0
5.0
k
pF
Stray Tuning Capacitance (Pin 3 to ground)
Effective Oscillator Source Impedance (Pin 3 to load)
5.0
2.0
pF
k
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3MOTOROLA ANALOG IC DEVICE DATA
Figure 2. TV Modulator
BiasSection
FM Oscillator/Modulator
Audio InSound Carrier
OSC B+Sound Carrier
Oscillator VCC
AM Modulator
RF Out
AM Oscillator
RF Tank
14 4 3 2 8 9 7 6
R10 R11 R126.0k
R16
Q1 Q2
R13325
Q25
Q24
Q23
D1
R15
R14Q3
Q4 Q5
Q6
C1
R17
Q7
Q12 Q13 Q14 Q15
Q21
Q22
Q10 Q11
Q26 Q27 Q8 Q9 Q16 Q17Q18
R1 R2 R3 R4 R5 R6 R7 R8 R9
5 1 13 12 11
Gnd Sound CarrierIn
Gain Video In
I
=1.15mA
2
Q19 Q20
I
=1.15mA
1 I
=1.15mA
1
GENERAL INFORMATION
The MC1374 contains an RF oscillator, RF modulator, and
a phase shift type FM modulator, arranged to permit good
printed circuit layout of a complete TV modulation system.
The RF oscillator is similar to the one used in MC1373, and is
coupled internally in the same way. Its frequency is controlled
by an external tank on Pins 6 and 7, or by a crystal circuit, and
will operate to approximately 105 MHz. The video modulator
is a balanced type as used in the well known MC1496.
Modulated sound carrier and composite video information
can be put in separately on Pins 1 and 11 to minimize
unwanted crosstalk. A single resistor on Pins 12 and 13 is
selected to set the modulator gain. The RF output at Pin 9 isa current source which drives a load connected from Pin 9 to
VCC.The FM system was designed specifically for the TV
intercarrier function. For circuit economy, one phase shift
circuit was built into the ship. Still, it will operate from 1.4 MHz
to 14 MHz, low enough to be used in a cordless telephone
base station (1.76 MHz), and high enough to be used as an
FM IF test signal source (10.7 MHz). At 4.5 MHz, a deviation
of 25 kHz can be achieved with 0.6% distortion (typical).
In the circuit above, devices Q1 through Q7 are active in
the oscillator function. Differential amplifier Q3, Q4, Q5, and
Q6 acts as a gain stage, sinking current from input section
Q1, Q2 and the phase shift network R17, C1. Input amplifier
Q1, Q2 can vary the amount of in phase Q4 current to be
combined with phase shifter current in load resistor R16. The
R16 voltage is applied to emitter follower Q7 which drives an
external LC circuit. Feedback from the center of the LC
circuit back to the base of Q6 closes the loop. As audio inputis applied which would offset the stable oscillatory phase, the
frequency changes to counteract. The input to Pin 14 can
include a dc feedback current for AFC over a limited range.
The modulated FM signal from Pin 3 is coupled to Pin 1 of
the RF modulator and is then modulated onto the AM carrier.
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MC1374
4MOTOROLA ANALOG IC DEVICE DATA
AM Section
The AM modulator transfer function in Figure 3 shows that
the video input can be of either polarity (and can be applied at
either input). When the voltages on Pin 1 and Pin 11 are
equal, the RF output is theoretically zero. As the difference
between VPin 11 and VPin 1 increases, the RF output
increases linearly until all of the current from both I1 current
sources (Q8 and Q9) is flowing in one side of the modulator.
This occurs when (VPin11 VPin1) = I1 RG, where I1 is
typically 1.15 mA. The peaktopeak RF output is the 2I1 RL.Usually the value of RL is chosen to be 75 to ease the
design of the output filter and match into TV distribution
systems. The theoretical range of input voltage and RG is
quite wide, but noise and available sound level limit the useful
video (sync tip) amplitude to between 0.25 Vpk and 1.0 Vpk.
It is recommended that the value of RG be chosen so that
only about half of the dynamic range will be used at sync tip
level.
The operating window of Figure 5 shows a crosshatched
area where Pin 1 and Pin 11 voltages must always be in order
to avoid saturation in any part of the modulator. The letter represents one diode drop, or about 0.75 V. The oscillator
Pins 6 and 7 must be biased to a level of VCC 2I1 RL (or
lower) and the input Pins 1 and 11 must always be at least 2below that. It is permissible to operate down to 1.6 V,
saturating the current sources, but whenever possible, the
minimum should be 3 above ground.
The oscillator will operate dependably up to about
105 MHz with a broad range of tank circuit component
values. It is desirable to use a small L and a large C to
minimize the dependence on IC internal capacitance. An
operating Q between 10 and 20 is recommended. The values
of R1, R2 and R3 are chosen to produce the desired Q and to
set the Pin 6 and 7 dc voltage as discussed above.
Unbalanced operation, i.e., Pin 6 or 7 bypassed to ground, is
not recommended. Although the oscillator will still run, and
the modulator will produce a useable signal, this mode
causes substantial baseband video feedthrough.Bandswitching, as Figure 1 shows, can still be accomplished
economically without using the unbalanced method.
The oscillator frequency with respect to temperature in the
test circuit shows less than 20 kHz total shift from 0 to 50C
as shown in Figure 7. At higher temperatures the slope
approaches 2.0 kHz/C. Improvement in this region would
require a temperature compensating tuning capacitor of the
N75 family.
Crystal control is feasible using the circuit shown in Figure
21. The crystal is a 3rd overtone series type, used in series
resonance. The L1, C2 resonance is adjusted well below the
crystal frequency and is sufficiently tolerant to permit fixed
values. A frequency shift versus temperature of less than
1.0 Hz/C can be expected from this approach. The resistorsRa and Rb are to suppress parasitic resonances.
Coupling of output RF to wiring and components on Pins 1
and 11 can cause as much as 300 kHz shift in carrier (at
67 MHz) over the video input range. A careful layout can
keep this shift below 10 kHz. Oscillator may also be
inadvertently coupled to the RF output, with the undesired
effect of preventing a good null when V11 = V1. Reasonable
care will yield carrier rejection ratios of 36 to 40 dB below sync
tip level carrier.
In television, one of the most serious concerns is the
prevention of the intermodulation of color (3.58 MHz) and
sound (4.5 MHz) frequencies, which causes a 920 kHz signal
to appear in the spectrum. Very little (3rd order) nonlinearity is
needed to cause this problem. The results in Figure 6 are
unsatisfactory, and demonstrate that too much of the
available dynamic range of the MC1374 has been used.
Figures 8 and 10 show that by either reducing standard
signal level, or reducing gain, acceptable results may beobtained.
At VHF frequencies, small imbalances within the device
introduce substantial amounts of 2nd harmonic in the RF
output. At 67 MHz, the 2nd harmonic is only 6 to 8 dB below
the maximum fundamental. For this reason, a double pi low
pass filter is shown in the test circuit of Figure 3 and works
well for Channel 3 and 4 lab work. For a fully commercial
application, a vestigial sideband filter will be required. The
general form and approximate values are shown in Figure 19.
It must be exactly aligned to the particular channel.
2I1RL
I1RG 0 +I1RG
Differential Input, V11V1 (V)
RFOutput
V(pp)
Figure 3. AM Modulator Transfer Function
Figure 4. AM Test Circuit
L1
R2470
0.001
VCC
C2 56
0.1H
RF
V1
10F+
VideoInput
1.0k
V11RG
22 47 22
1
11
12 13
9
8
76
5
470R3
R1470
RL
75
22H 22H
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5MOTOROLA ANALOG IC DEVICE DATA
Figure 5. The Operating Window Figure 6. 920 kHz Beat
Figure 7. RF Oscillator Frequency
versus Temperature Figure 8. 920 kHz Beat
Figure 9. RF Oscillator Frequency
versus Supply Voltage Figure 10. 920 kHz Beat
5.0 6.0 7.0 8.0 9.0 10 11 12
VCC
VCC, SUPPLY VOLTAGE (Vdc)AM
MODULATORINPU
TVOLTAGEPIN1ORPIN11(V
3
VCC 2I1RL
VCC 2I1RL
VCC 3 2I1RL
RecommendedV1 & V11
Operating Region
Absolute Min = 1.6 V(2 + Sat)
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4
b
a
DIFFERENTIAL INPUT (V11 V1) [Vdc)
(fc
920kHz)AMPLITUDE
(fc)AMPLITUDE
[dB]
Initial Video = 1.0 VdcChroma (3.58 MHz) = 300 mVppSound (4.5 MHz) a) = 250 mVpp
b) = 500 mVppGain Resistor RG = 1.0 k
0 25 50 75 100
TA, AMBIENT TEMPERATURE (C)
FREQUENCYSHIFT(kHz)
b
a
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4
DIFFERENTIAL INPUT (V11 V1) [Vdc)
(fc)AMPLITUDE
[dB] Initial Video = 0.5 VdcChroma (3.58 MHz) = 150 mVpp
Sound (4.5 MHz) a) = 125 mVppb) = 250 mVpp
Gain Resistor RG = 1.0 k
5.0 6.0 7.0 8.0 9.0 10 11 12
VCC, SUPPLY VOLTAGE (V)
NORMALIZEDFREQUENCY(kHz)
b
a
0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.5 1.6 1.8 2.0 2.2 2.4 2.8
DIFFERENTIAL INPUT (V11 V1) [Vdc)
[dB]
Initial Video = 1.0 VdcChroma (3.58 MHz) = 300 mVppSound (4.5 MHz) a) = 250 mVpp
b) = 500 mVppGain Resistor (RG) = 2.2 k
RL = 75 I1 = 1.15 mA
(fc
920kHz)AMPLITUDE
(fc
920kHz)AMPLITUDE
(fc)AMPLITUDE
12
11
10
9.0
8.0
7.0
6.0
5.0
4.0
3.0
2.0
1.0
0
0
10
20
30
40
50
60
70
80
10
0
10
20
30
40
50
60
70
0
10
20
30
40
50
60
70
80
10
0
10
20
30
40
50
60
70
0
10
20
30
40
50
60
70
80
TA = 25C
fc = 61.25 MHz
fc
61.25 MHzVCC = 12 Vdc
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MC1374
6MOTOROLA ANALOG IC DEVICE DATA
FM Section
The oscillator center is approximately the resonance of the
inductor L2 from Pin 2 to Pin 3 and the effective capacitance
C3 from Pin 3 to ground. For overall oscillator stability, it is
best to keep XL in the range of 300 to 1.0 k.
The modulator transfer characteristic at 4.5 MHz is shown
in Figure 15. Transfer curves at other frequencies have a very
similar shape, but differ in deviation per input volt, as shown in
Figures 13 and 17.
Most applications will not require DC connection to theaudio input, Pin 14. However, some improvements can be
achieved by the addition of biasing circuitry. The unaided
device will establish its own Pin 14 bias at 4 , or about 3.0 V.
This bias is a little too high for optimum modulation linearity.
Figure 14 shows better than 2 to 1 improvement in distortion
between the unaided device and pulling Pin 14 down to 2.6 V
to 2.7 V. This can be accomplished by a simple divider, if the
supply voltage is relatively constant.
The impedance of the divider has a bearing on the
frequency versus temperature stability of the FM system. A
divider of 180 k and 30 k (for VCC = 12 V) will give good
temperature stabilization results. However, as Figure 18
shows, a divider is not a good method if the supply voltage
varies. The designer must make the decisions here, basedon considerations of economy, distortion and temperature
requirements and power supply capability. If the distortion
requirements are not stringent, then no bias components are
needed. If, in this case, the temperature compensation needs
to be improved in the high ambient area, the tuning capacitor
from Pin 3 to ground can be selected from N75 or N150
temperature compensation types.
Another reason for DC input to Pin 14 is the possibility of
automatic frequency control. Where high accuracy of
intercarrier frequency is required, it may be desirable to feed
back the DC output of an AFC or phase detector for nominal
carrier frequency control. Only limited control range could be
used without adversely affecting the distortion performance,
but very little frequency compensation will be needed.One added convenience in the FM section is the separate
Pin oscillator B+ which permits disabling of the sound
system during alignment of the AM section. Usually it can be
hard wired to the VCC source without decoupling.
Standard practice in television is to provide preemphasis
of higher audio frequencies at the transmitter and a matching
deemphasis in the TV receiver audio amplifier. The purpose
of this is to counteract the fact that less energy is usually
present in the higher frequencies, and also that fewer
modulation sidebands are within the deviation window. Both
factors degrade signal to noise ration. Preemphasis of 75 s
is standard practice. For cases where it has not been
provided, a suitable preemphasis network is covered in
Figure 20.It would seem natural to take the FM system output from
Pin 2, the emitter follower output, but this output is high in
harmonic content. Taking the output from Pin 3 sacrifices
somewhat in source impedance but results in a clean output
fundamental, with all harmonics more than 40 dB down. This
choice removes the need for additional filtering components.
The source impedance of Pin 3 is approximately 2.0 k, and
the open circuit amplitude is about 900 mV pp for the test
circuit shown in Figure 11.
The application circuit of Figure 1 shows the
recommended approach to coupling the FM output from Pin 3
to the AM modulator input, Pin 1. The input impedance at Pin
1 is very high, so the intercarrier level is determined by the
source impedance of Pin 3 driving through C4 into the video
bias circuit impedance of R4 and R5, about 2.2 k. Thisprovides an intercarrier level of 500 mV pp, which is correct
for the 1.0 V peak video level chosen in this design. Resistor
R6 and the input capacitance of Pin 1 provide some
decoupling of stray pickup of RF oscillator or AM output which
may be coupled to the sound circuitry.
C3
(pF)
fo(MHz)
L2
(H)
10.7 12 10
4.5 120 10
402001.76
VCC
C140.01F
IntercarrierSound Output
(Use FET Probe)
L210H
C3120pF
C5
0.001F
7
6
5
4
3
2
1
8
9
10
11
12
13
14
R12
R13
AudioInput
C61F
Optional Bias R(See Text)
+
Figure 11. FM Test Circuit
1.4 2.0 3.0 5.04.0 6.0 7.0 8.0 9.0 10 14
fosc, OSCILLATOR FREQUENCY [MHz]
MAXIM
UMCENTER-FREQUENCY
SLO
PE(
f/
V
)(MHz/V)
in
TA = 25C
Figure 12. Modulator Sensitivity
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
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7MOTOROLA ANALOG IC DEVICE DATA
fosc,OSCILLATORFREQUENCY(MHz)
Figure 13. Modulator Transfer Function Figure 14. Distortion versus Modulation Depth
Figure 15. Modulator Transfer FunctionFigure 16. FM System Frequency
versus Temperature
Figure 17. Modulator Transfer Function Figure 18. FM System Frequency versus VCC
4.0 5.0 6.0 7.0 8.0 9.0 10 11 12
VCC, SUPPLY VOLTAGE (Vdc)
0 1.0 2.0 3.0 4.0 5.0 6.0 7.0
DC INPUT VOLTAGE, PIN 14 (V)
f
0 1.0 2.0 3.0 4.0 5.0 6.0 7.0
DC INPUT VOLTAGE, PIN 14 (V)
0 1.0 2.0 3.0 4.0 5.0 6.0 7.0
DC INPUT VOLTAGE, PIN 14 (V)
12 V9.0 V VCC5.0 V
0 25 50 75 100
DEVIATION (kHz)
DIST
ORTION(%)
VCC = 12 VTA = 25Cfc = 4.5 MHz
0 25 50 75 100
TA, AMBIENT TEMPERATURE (C)
f,FREQUENCY(MHz)
f,FREQU
ENCY(MHz)
osc,OSCILLATORFREQUENCY(MHz)
fosc,OSCILLATO
RFREQUENCY(MHz)
2.1
2.0
1.9
1.8
1.7
1.6
1.5
1.4
1.3
5.0
4.0
3.0
2.0
1.0
0
4.9
4.8
4.7
4.6
4.5
4.4
4.3
4.2
4.1
4.55
4.54
4.53
4.52
4.51
4.50
4.49
4.48
4.47
11.6
11.2
11.0
10.6
10.4
10.2
10.0
9.8
9.6
10.8
11.4
4.50
4.49
4.48
4.47
4.46
4.45
4.44
4.43
4.42
TA = 25C(1.76 MHz)
VCC = 12 V
VCC = 5.0 V, 9.0 V
Self Bias (2.93.0 V)
Optimum Bias (2.62.7 V)
TA = 25C(4.5 MHz) VCC = 12 V
VCC = 5.0 V, 9.0 V
VCC = 12 V
Pin 14 V to 2.6 V
180 k/30 k Divider
Pin 14 Open
TA = 25C(10.7 MHz)
Pin 14 to 2.6 V Source
Pin 14 Open
Pin14 180 k/ 30 k Divider
TA = 25C
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8MOTOROLA ANALOG IC DEVICE DATA
Figure 19. A Channel 4 Vestigial Sideband Filter
Figure 20. Audio PreEmphasis Circuit
Figure 21. Crystal Controlled RF Oscillator
for Channel 3, 61.25 MHz
NOTE: See Application Note AN829 for further information.
VCC
8
9 RL = 75
2.7k39pF
33pF
8.2pF
100
Output75
Both transformer windings4T #23 AWGclose wound on 1/4IDon common axis, 3/8spacing.
8T #23 AWGclose wound on 1/8ID,knife tuned to trap Channel 361.25 MHz.
2424
33pF
33pF
24
8.2pF
0
1020
30
4050
6070
61 65 69 73
Ch. 4Pix
Ch. 4S
f, FREQUENCY (MHz)
AT
TENUATION(dB)
FlatAudioInput
CC = 0.1FC = 0.0012F
r = 56k6.0k
R
14
AudioInput
5 Gnd
+
25
20
15
10
5
0
521 210 2100 21k
2 RC
1
2 (r + R)CC
1
f, FREQUENCY (MHz)
2 (2100 Hz)
1Preemphasis = 75 s = rC =
2 rC
1
VCC
C10.001
R1 470
R2R3
61.252MHz C2
56pFRa
180
Rb 18
L1
76
0.15H
470470
MC1374
RELATIVEOUTPUT/IN
PUT(dB)
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9MOTOROLA ANALOG IC DEVICE DATA
OUTLINE DIMENSIONS
NOTES:1. LEADS WITHIN 0.13 (0.005) RADIUS OF TRUE
POSITION AT SEATING PLANE AT MAXIMUMMATERIAL CONDITION.
2. DIMENSION L TO CENTER OF LEADS WHENFORMED PARALLEL.
3. DIMENSION B DOES NOT INCLUDE MOLDFLASH.
4. ROUNDED CORNERS OPTIONAL.
1 7
14 8
B
A
F
H G DK
C
N
L
J
M
SEATINGPLANE
DIM MIN MAX MIN MAX
MILLIMETERSINCHES
A 0.715 0.770 18.16 19.56B 0.240 0.260 6.10 6.60C 0.145 0.185 3.69 4.69D 0.015 0.021 0.38 0.53F 0.040 0.070 1.02 1.78G 0.100 BSC 2.54 BSCH 0.052 0.095 1.32 2.41J 0.008 0.015 0.20 0.38K 0.115 0.135 2.92 3.43
L 0.300 BSC 7.62 BSCM 0 10 0 10N 0.015 0.039 0.39 1.01
_ _ _ _
P SUFFIXPLASTIC PACKAGE
CASE 64606ISSUE L
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10MOTOROLA ANALOG IC DEVICE DATA
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