majority logic decoding -...
TRANSCRIPT
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Ammar Abh-Hhdrohss Islamic University -Gaza ١
Majority Logic Decoding
Slide ٢Channel Coding Theory
One Step majority logic decoding
Consider C as an (n, k) cyclic code with parity check matrix H. His an (n, n - k) which generate the dual code ,denoted by Cd.
For any code v in C and w in Cd, the inner product of v and w is zero; that is ,
Now, suppose that a codeword v in c is transmitted. Let e = (e0, e1, …., en-1) and r = (r0, r1, …., rn-1) be the error vector and the received vector, respectively.
Then, r = v + e
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Slide ٣Channel Coding Theory
One Step majority logic decoding
For any vector w in the dual code Cd, we can form the following
Which is called a parity check sum. A must be zero for no errors. If there is an error then A is equal to
Suppose that there is J vectors in the dual code Cd,
Slide ٤Channel Coding Theory
One Step majority logic decoding
That have the following properties1) the (n-1) component of each vector is 1; that is
2) For i ≠ n – 1 , there is at most one vector whose i th component is a 1. For example if w1,i = 1, then w2,i = w3,i = … = wJ,i = 0.
I.E these vector are orthogonal on the n -1 digital position.
So we can form the following check-sums
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Slide ٥Channel Coding Theory
One Step majority logic decoding
Using the first properties, and w.r = w.e, we can rewrite previous equation as
Using 2nd property of w then
Slide ٦Channel Coding Theory
From previous equation en -1 can be decoded correctly based on majority if there is j/2 errors has happened.
Example: Consider a (15, 7) cyclic code generated by the polynomial
The parity check on systematic form is found to as follows
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Slide ٧Channel Coding Theory
Consider the following linear combinations of rows of H,
if the received error vector is r, then
It is clear that if two errors happen or less e14 can be decoded correctly
Slide ٨Channel Coding Theory
Steps for majority decoding
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Slide ٩Channel Coding Theory
For our example
Slide ١٠Channel Coding Theory
TYPE I
The parity check sum on error digit can be formed from the syndrome digits:
H is the parity check matrix on the systematic form.
As the orthogonal vectors w1, w2,…, wj are vectors in the row space of H, they are linear combination of rows of H.
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Slide ١١Channel Coding Theory
This implies:
Because of the systematic structure of H, it can be seen
Let r = (r0, r1, …, rn-1) be the received vector. Then the syndrome of r is :
Where the ith syndrome digit
Slide ١٢Channel Coding Theory
Now, consider the parity-check sum
or
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Slide ١٣Channel Coding Theory
Steps of type – I majority logic decoding
Step1 : the syndrome is computed using the shift of the received polynomial.
Step 2: the J-parity check sums orthogonal on en-1 are form by taking the proper sum of the syndrome digits. These check-sum are fed to the majority logic circuit.
Step 3: the first received digit is corrected. And the syndrome is shifted to correct the next diigt.
Step 4: step 2 and 3 is applied on the new syndrome to correct rn-2
Step 5: the process is repeated until all received digits are corrected.
Slide ١٤Channel Coding Theory
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Slide ١٥Channel Coding Theory
Example
Consider the (15, 7) BCH code given in Example 8.1 from w1, w2, w3, and w4 that are orthogonal on the digit position 14.
We find that the parity check orthogonal on e14 are equal to
Based on these sums, we construct the type I one-step majority logic decoder shown at the next slide.
If (0, 0, …. , 0) is transmitted and r (x) = x 13 + x 14 is received.
By shifting the received sequence the syndrome register contains (0 0 1 1 1 0 0 1).
Slide ١٦Channel Coding Theory
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Slide ١٧Channel Coding Theory
The four parity check sums orthogonal
So the majority decoder decide e14 = 1;
The buffer register is shifted once and the new parity check sums are
So the majority decoder decide e13 = 1;
The next thirteen bits are error free (you can check by shifting again and again)
Slide ١٨Channel Coding Theory
Class of one step majority logic decodable codes
Let C be a (n , k) cyclic code generated by g (x), where n = 2m – 1. we extend the vector v = (v0, v1, … , v n-1) by adding overall parity bit v∞ where,
And the codeword of the extended code, Ce ,become
Now if we assign 0 to v∞ and to v0 , 2 to v1 , Or the component vi is numbered i.
110 .... nvvvv
110 ,,,, nvvvv
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Slide ١٩Channel Coding Theory
We can do permutation of the location using Z = aY + b Where Y is location of component ve , and a, b are constants.
This permutation is called affine permutation Example
Slide ٢٠Channel Coding Theory
An extended cod Ce of length 2m is said to be invariant under the group of affine permutation if every affine permutation carries the codeword in Ce into another codeword in Ce.
Let h be a nonnegative integer less than 2m. The radix-2 expansion of h is
Where i = 0 or 1. let h’ be another nonnegative integer less than 2m whose radix 2 expansion is
The integer h ’ is said to be a descent of h if
11
2210 222
mmh
11
2210 222
mmh
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Slide ٢١Channel Coding Theory
For example for m = 5, all the numbers 0, 1, 4, 5, 16, 17, 20 are descendants of 21.
(h) denotes the set of all nonzero proper descendants of h,
The extended code Ce is invariant under affine permutation if and only if for every h that is a root of the generator polynomial g (x) of C and for every h ’ in (h), h’ is also a root of g (x) and 0 is not a root of g (x).
The generator polynomial is said to have doubly transitive invariant (DTI) property.
If Ce is invariant under affine permutation, then C is a cyclic code (HOW?)
Slide ٢٢Channel Coding Theory
Now, it is the time to present a class of one-step majority-logic decodable codes whose dual codes have the DTI property.
Let J and L be two factors of 2m – 1 such that 2m – 1 = JL, then
Let
But
Which yields the polynomial has roots
112 mJL
1JX LJLL 120 ,,,,
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Slide ٢٣Channel Coding Theory
To form H (x) we notice that H (x) has h as a root only if 1) h is a root of (x) 2) for every h’ in (h) h’ is also a root of (x) .
Let i be a root of h(x) and i(x) is the minimal polynomial of i
.
Or
The generator polynomial of C is
Slide ٢٤Channel Coding Theory
So first we need to determine J vectors from C’ that are orthogonal on the digit location
(x) is a code polynomial in C’ generated by H (x).
This imply that x(x) , x2(x) , …., xJ-1(x) are also code polynomials of C’.
But for i ≠ j implies xi(x) and xj(x) do not have any common terms.
So by adding an overall parity bit to each of these vectors, we obtain J vectors u0, u1, …, uj-1
12 m
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Slide ٢٥Channel Coding Theory
The J vectors are orthogonal on the digit location ∞. Now, we apply the affine permutation
To the vectors u0, u1, …, uj-1 to achieve z0, z1, …, zj-1 which are also in C’e.
But the permutation carries the component ui at location ∞ to the location
The final step is to delete the locations ∞ from z0, z1, …, zj-1and we can form the J check sums from the resultant vectors.
Therefore the cyclic code generated by Can correct up to J/2. this is called type-0
22 m
YZ
22 m
Slide ٢٦Channel Coding Theory
Example
Let m = 5 , the factorization applies as
Thus J = 5, L = 3 and
10551512 11114
XXXXX
1051 XXx
129635 ,,,1, rootshas1 X
1413111087542105 ,,,,,,,,, rootshas1 XX
8542 ,,,, rootshas XH
8421 ,,, forpolynomialminimaltheis X
1055 , forpolynomialminimaltheis X
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Slide ٢٧Channel Coding Theory
Then H (x) can be calculated as
It can be easily checked that H (x) divides (x) and divides x15 + 1.
Thus
H(x) generates C’ where (x) ,x(x) , x2(x) , …., xJ-1(x) are code polynomials in C’.
2451 11 xxxxxxxH
65431 xxxxxH
985431 xxxxxxG
Slide ٢٨Channel Coding Theory
The dual code C is generated by
The vectors (x) ,x(x) , x2(x) , …., xJ-1(x) are given as
Adding the overall parity bit we get
965419 1)( xxxxxxGxxg
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Slide ٢٩Channel Coding Theory
Applying the affine permutation Z = Y+ 14
Slide ٣٠Channel Coding Theory
Deleting the overall parity bit
These vector are orthogonal on the digit location 14. Let r = (r0, r1, r2, r3, r4, r5, r6, r7, r8, r9, r10, r11, r12, r13, r14) .
The parity check sums orthogonal on e14 are
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Slide ٣١Channel Coding Theory
The C is capable of correcting 2 errors