lecture 5: resonance
TRANSCRIPT
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5
Lecture 5: Resonance
Prof. J. S. Smith
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Context
In the last lecture, we discussed simple zeros and poles of a transfer function, and creating approximate Bode plots for hand plotting of phase and magnitude characteristics.Is this lecture, we will discuss second order transfer functions, circuits which have resonances.
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Second Order Circuits
The series resonant circuit is one of the most important elementary circuits:
This model is not only useful for physical LCR circuits, but also approximates mechanical resonances, molecular resonance, microwave cavities, transmission lines, buildings, bridges, …
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Time Domain analysis
The differential equations for this circuit are:
dttdiLtv L
L)()( =
rtitv rr ⋅= )()(
dttdvCti C
c)()( =
dttdvRCtv
dtdt
tdvCdLv
tvtvtvtv
CC
C
s
RCLs
)()(
)()()()()(
++⎟⎠⎞
⎜⎝⎛
=
++=
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
So the differential equation for the circuit is:
Let’s see how this circuit responds to a step input, zero before time t=0, and Vdd for t>0
First of all, note that the steady state solution is
dttdvRCtvtv
dtdLCtv C
CCs)()()()( 2
2
++=
dds Vtv =∞→ )(
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Transient solution
To find the transient solution, for t>0, let’s try a solution of the form:
– Where s is a complex number
Now we substitute this into our D. E.:
Giving us a second order equation for s:
ddst
C VAetv +=)(
ststdd
stdd
CCCs
RCsAeAeVAeLCsVdt
tdvRCtvtvdtdLCtv
+++=
++=
2
2
2 )()()()(
RCsLCs ++= 10 2
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
We can use the quadratic formula to find solutions for s: →
If s is real, then the circuit is overdamped, and the voltage will change exponentially to its steady state value.If s is complex, the circuit is underdamped, and the solution will oscillate around the steady state value before settling down to it.
RCsLCs ++= 10 2
⎟⎠⎞
⎜⎝⎛−⎟
⎠⎞
⎜⎝⎛±=
LCLR
LRs 1
22
2
2,1
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Underdamped caseFor the underdamped case:
We will need to take sums of the complex exponentials to get real solutions, solutions are of the form:
Where: and
and A and are determined by the boundary conditions
2
2,1 21
2⎟⎠⎞
⎜⎝⎛−⎟
⎠⎞
⎜⎝⎛±=
LR
LCj
LRs
)sin()( 1 φωα ++= − tAeVtv tddC
2
21
⎟⎠⎞
⎜⎝⎛−⎟
⎠⎞
⎜⎝⎛=
LR
LCω
LR
2=α
φ
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. SmithResponse of underdamped circuit to step
If the circuit is moderately damped:
0.5 1 1.5 2 2.5 3
0.25
0.5
0.75
1
1.25
1.5
1.75
2
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Underdamped response to step
And if very underdamped:
0.5 1 1.5 2 2.5 3
0.25
0.5
0.75
1
1.25
1.5
1.75
2
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Underdamped Oscillations:
In the very underdamped case (R small), the ringing dies exponentially in a time:
And each oscillation takes a time:
So the number of oscillations of ringing that will occur is approximately:
RL21 =−α
πππω
2212)2(
12
1 LCL
RLC
≈⎟⎟
⎠
⎞
⎜⎜
⎝
⎛⎟⎠⎞
⎜⎝⎛−⎟
⎠⎞
⎜⎝⎛=
−
−
CL
RLC
RLN
ππ1
22 =≈
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Frequency domain analysisWith phasor analysis, this circuit is readily analyzed, for example, the input impedance:
You can also write the expression for the voltage across any component
RCj
LjZ ++=ω
ω 1
⎟⎠⎞
⎜⎝⎛ −+=++=
LCLjRR
CjLjZ 2
111ω
ωω
ω
Z
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Series LCR Impedance
For example, the voltage across the capacitor:
SCCc VRCj
LjCj
ZIV1
11−
⎟⎟⎠
⎞⎜⎜⎝
⎛++==
ωω
ω
Z
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Low frequency behavior
At low frequencies, the characteristic of this circuit is dominated by the capacitor
The inductor looks like a shortat low frequencies
The ω in the denominator of theterm for the capacitor makes it the major contribution
RCj
LjZ ++=ω
ω 1
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
High frequency behavior
At high frequencies, the characteristics of this circuit are dominated by the inductor
The capacitor looks like a short at low frequencies
The ω proportionality of theterm for the inductor makes it the major contribution
RCj
LjZ ++=ω
ω 1
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Near resonanceNear resonance, energy will oscillate between the capacitor and the inductor
Notice that the terms for thecapacitor and the inductor haveopposite sign, so they can add upto zero impedance at one frequency At that frequency (ω0=[LC] -1/2) , energy is perfectlyoscillating between the inductor and the capacitor,→The only impedance left at that frequency is the resistor.
RCj
LjZ ++=ω
ω 1
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
At resonance
LC12 =ω
01]Im[ =⎟⎟⎠
⎞⎜⎜⎝
⎛+=
CjLjZ
ωω
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Power sidebar
The power into a circuit is just the voltage times the current, but remember this is not linear, so we’ll go back to complete notation:
ZIV
eIeIti
eVeVtv
tjtj
tjtj
=
+=
+=
−
−
ˆˆ
)*ˆˆ(21)(
)*ˆˆ(21)(
ωω
ωω
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Convert from phasors, then multiply
Power:
( )( ) ( ))*ˆ*ˆ()ˆˆ(
41)ˆ*ˆ(*)ˆˆ(
41
)*ˆ*ˆ()ˆ*ˆ(*)ˆˆ()ˆˆ(41
)*ˆ*ˆ()ˆ*ˆ(
)*ˆˆ()ˆˆ(41
)*ˆˆ)(**ˆˆ(41
)*ˆˆ)(*ˆˆ(41)()(
22
22
tjtj
tjtj
tjtjtjtj
tjtjtjtj
tjtjtjtj
tjtjtjtj
eIVeIVIVIVP
eIVIVIVeIVP
eIeVeIeV
eIeVeIeVP
eIeVeZIeVP
eIeIeVeVtitvP
ωω
ωω
ωωωω
ωωωω
ωωωω
ωωωω
−
−
−−−
−
−−
−−
+++=
+++=
⎟⎟⎠
⎞⎜⎜⎝
⎛
++
+=
++=
++=⋅=
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Expression for Power from ZPower:
Notice that the second and fourth terms are just the complex conjugate of the first and third, so we can write:
The second term averages to zero, so the first term gives us the average power
( ) ( )( ) ( ))*ˆ**ˆ()ˆˆ(
41)ˆ**ˆ(*)ˆˆ(
41
)*ˆ*ˆ()ˆˆ(41)ˆ*ˆ(*)ˆˆ(
41
22
22
tjtj
tjtj
eIZIeIZIIZIIZIP
eIVeIVIVIVP
ωω
ωω
−
−
+++=
+++=
{ } { }tjeIZIREIZIREP ω2ˆˆ21*ˆˆ
21
+=
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Reactive PowerLet’s take the phase angle of the current to be zero, to make it simpler:
Now look at the second term:
The first term is unavoidable ripple in the power, since this is AC, but the imaginary part of Z is power which goes in at one part of the cycle, and then is returned at a later point. This is called reactive power.
( ){ }
( ))2sin()2(cos(21
)2sin()2cos(21
22
22
tZtZIP
tjtZREIP
ir ωω
ωω
−=
+=
{ }⎟⎠⎞
⎜⎝⎛ += tj
r ZeREZIP ω22
21
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Resonance
At resonance the circuit impedance is purely real The reactive power for the Cap is supplied from the inductor, and visa versa.Imaginary components of impedance cancel outFor a series resonant circuit, the current is maximum at resonance
+VR
−
+ VL – + VC –
+Vs
−
VL
VC
VR
Vs
0ωω <
VL
VC
VRVs
0ωω =
VC
VL
VR
Vs
0ωω >
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Series Resonance Voltage Gain
At resonance, the voltage across the inductor, and across the capacitor, can be larger than the voltage of the voltage source:
Remember:
+VR
−
+ VL – + VC –
s
ssL
VjQ
LjRVLj
ZVLjIV
⋅=
=== 000
0 )(ωω
ωω
s
ssC
VjQ
LjRV
jL
ZV
CjIV
⋅−=
−=== 00
00 )(1 ωω
ωω
RZ
RCL
RCLC
RCRLQ 0
0
0 1111=====
ωω
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Second Order Transfer FunctionSo we have:
To find the poles/zeros, let’s put the H in canonical form:
One zero at DC frequency can’t conduct DC due to capacitor
RCj
Lj
RVVjH
s ++==
ωω
ω 1)( 0+Vo
−
RCjLCCRj
VVjH
s ωωωω+−
== 20
1)(
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Poles of 2nd Order Transfer Function
Denominator is a quadratic polynomial:
LRjj
LC
LRj
RCjLCCRj
VVjH
s ωω
ω
ωωωω
++=
+−==
22
0
)(11)(
LRjj
LRj
jHωωω
ωω
++=
220 )(
)(LC12
0 ≡ω
Qjj
Qj
jH022
0
0
)()( ωωωω
ωω
ω++
=R
LQ 0ω≡
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Finding the poles…
Let’s factor the denominator:
Poles are complex conjugate frequencies
Re
Im
0)( 20
02 =++ ωωωωQ
jj
22 −±−=−±−=Q
jQQQ 4
11242 0
020
200 ωωωωωω
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Resonance without Loss
The transfer function can be parameterized in terms of loss. First, take the lossless case, R=0:
When the circuit is lossless, the poles are at realfrequencies, so the transfer function blows up!At this resonance frequency, the circuit has zero imaginary impedance and thus zero total impedanceEven if we set the source equal to zero, the circuit can have a steady-state response
Re
Im
020
200
42ωωωωω j
QQQ
±=⎟⎟⎠
⎞⎜⎜⎝
⎛−±−=
∞→
2
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Magnitude Response
How peaked the response is depends on Q
Qj
Qj
LRj
LRj
jH022
0
0
0
0220
0
0
)( ωωωω
ωω
ωωωωω
ωωω
ω+−
=+−
=
1=Q
10=Q
100=Q
0ω
1)(0
020
20
20
0 =+−
=
Qj
Qj
jH ωωωω
ω
ω
1)( 0 =ωjH
0)0( =H
ω∆
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
How Peaky is it?
Let’s find the points when the transfer function squared has dropped in half:
( ) 21)( 2
02220
20
2 =
⎟⎟⎠
⎞⎜⎜⎝
⎛+−
⎟⎟⎠
⎞⎜⎜⎝
⎛
=
Q
QjH
ωωωω
ωωω
21
1/
1)( 2
0
220
2 =
+⎟⎟⎠
⎞⎜⎜⎝
⎛ −=
Q
jH
ωωωω
ω
1/
2
0
220 =⎟⎟
⎠
⎞⎜⎜⎝
⎛ −Qωωωω
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Half Power Frequencies (Bandwidth)
We have the following:
1/0
220 ±=−
Qωωωω
020
02 =−ωωωωQ
m
abbaQQ
>±±=+⎟⎟⎠
⎞⎜⎜⎝
⎛±±= 2
0
200
42ωωωω
Q0ωωωω =−=∆ −+
1/
2
0
220 =⎟⎟
⎠
⎞⎜⎜⎝
⎛ −Qωωωω
Q1
0
=∆ωω
Four solutions!
0000
<−−>+−<−+>++
babababa
Take positive frequencies:
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
More “Notation”
Often a second-order transfer function is characterized by the “damping” factor as opposed to the “Quality” factor
0)( 0220 =++
Qjj ωωωω
0)(1 2 =++Q
jj ωτωτ 0
1ω
τ =
02)()(1 2 =++ ζωτωτ jj
ζ21
=Q
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Second Order Circuit Bode Plot
Quadratic poles or zeros have the following form:
The roots can be parameterized in terms of the damping ratio:
012)()( 2 =++ ζωτωτ jj
22 )1(12)()(1 ωτωτωτζ jjj +=++⇒=
damping ratio
Two equal poles
1
)1)(1(12)()(12
212
−±−=
++=++⇒>
ζζωτ
ωτωτζωτωτζ
j
jjjj
Two real poles
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Bode Plot: Damped Case
The case of ζ >1 and ζ =1 is a simple generalization of simple poles (zeros). In the case that ζ >1, the poles (zeros) are at distinct frequencies. For ζ =1, the poles are at the same real frequency:
22 )1(12)()(1 ωτωτωτζ jjj +=++⇒=22 1)1( ωτωτ jj +=+
ωτωτ jj +=+ 1log401log20 2
( ) ( ) ( )ωτωτωτωτ jjjj +∠=+∠++∠=+∠ 1211)1( 2
AsymptoticSlope is 40 dB/dec
Asymptotic Phase Shift is 180°
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Underdamped Case
For ζ <1, the poles are complex conjugates:
For ωτ << 1, this quadratic is negligible (0dB)For ωτ >> 1, we can simplify:
In the transition region ωτ ~ 1, things are tricky!
22
2
11
012)()(
ζζζζωτ
ζωτωτ
−±=−±−=
=++
jj
jj
ωτωτζωτωτ log40)(log2012)()(log20 22 =≈++ jjj
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Underdamped Mag Plot
ζ=1
ζ=0.01
ζ=0.1ζ=0.2ζ=0.4
ζ=0.6ζ=0.8
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Underdamped Phase
The phase for the quadratic factor is given by:
For ωτ < 1, the phase shift is less than 90°For ωτ = 1, the phase shift is exactly 90°For ωτ > 1, the argument is negative so the phase shift is above 90° and approaches 180°Key point: argument shifts sign around resonance
( ) ⎟⎟⎠
⎞⎜⎜⎝
⎛−
=++∠ −2
12
)(12tan12)()(ωτωτζζωτωτ jj
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Phase Bode Plot
ζ=0.010.10.20.40.60.8
ζ=1
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Bode Plot GuidelinesIn the transition region, note that at the breakpoint:
From this you can estimate the peakiness in the magnitude response Example: for ζ=0.1, the Bode magnitude plot peaks by 20 log(5) ~14 dBThe phase is much more difficult. Note for ζ=0, the phase response is a step functionFor ζ=1, the phase is two real poles at a fixed frequencyFor 0<ζ<1, the plot should go somewhere in between!
Qjjjj 1212)()(12)()( 22 ==++=++ ζζζωτωτ
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Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Energy Storage in “Tank”
At resonance, the energy stored in the inductor and capacitor are
tLItiLw ML 0222 cos
21))((
21 ω==
tC
ItC
IC
diC
CtvCw
MM
C
02
20
2
02
220
2
22
sin21sin
21
)(121))((
21
ωω
ωω
ττ
==
⎟⎠⎞
⎜⎝⎛== ∫
LItC
tLIwww MMCLs2
02
20
022
21)sin1cos(
21
=+=+= ωω
ω
LIWW MSL2
max, 21
==
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Energy Dissipation in Tank
Energy dissipated per cycle:
The ratio of the energy stored to the energy dissipated is thus:
0
2 221
ωπ
⋅=⋅= RITPw MD
ππω
ωπ 22
12
21
21
0
0
2
2
QR
L
RI
LI
ww
M
M
D
S ==⋅
=
21
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
Physical Interpretation of Q-FactorFor the series resonant circuit we have related the Q factor to very fundamental properties of the tank:
The tank quality factor relates how much energy is stored in a tank to how much energy loss is occurring.If Q >> 1, then the tank pretty much runs itself … even if you turn off the source, the tank will continue to oscillate for several cycles (on the order of Q cycles)Mechanical resonators can be fabricated with extremely high Q
D
S
wwQ π2=
Department of EECS University of California, Berkeley
EECS 105 Spring 2004, Lecture 5 Prof. J. S. Smith
thin-Film Bulk Acoustic Resonator (FBAR)RF MEMS
Agilent Technologies(IEEE ISSCC 2001)Q > 1000Resonates at 1.9 GHz
Can use it to build low power oscillator
C0
Cx Rx Lx
C1 C2R0
Pad
Thin Piezoelectric Film