fundamental issues of power...
TRANSCRIPT
![Page 1: Fundamental Issues of Power Integritycc.ee.ntu.edu.tw/~rbwu/rapid_content/course/pi/PI2_Fundamental.pdf · R. B. Wu 0 0.5 1 1.5 2 2.5 3 3.5 4 1999 2000 2001 2002 2003 2004 2005 GHz](https://reader033.vdocuments.site/reader033/viewer/2022042310/5ed78fa767b53e06555d2271/html5/thumbnails/1.jpg)
Fundamental Issues of
Power Integrity
Textbook, Sec. 1.1 ~ 1.3
1
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R. B. Wu
Outline
Challenges of System Integration
Technology Scaling in Transistors
Functioning of Transistors
Power Delivery Network
Power Supply Noise
Target Impedance
Outline
2
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Challenges of
System Integration
3
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R. B. Wu
0
0.5
1
1.5
2
2.5
3
3.5
4
1999 2000 2001 2002 2003 2004 2005
GH
z
0
0.2
0.4
0.6
0.8
1
1.2
1.4
1.6
1.8
2
Vo
lts
Clock Frequency Bus Frequency Supply Voltage
(data from International Technology Roadmap for Semiconductors - http://public.itrs.net) 4
System Faster but Lower Margin
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R. B. Wu
Structure More Complicated
5
Transistors
Moore’s Law
http://www.embedded.com/design/programming-languages-and-tools/4375996/Using-Java-for-multicore-programming-complexity--Part-1
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R. B. Wu
Multi-Core CPU
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R. B. Wu
Wire Problem? D
ela
y (
ps)
R. Ho, K. W. Mai, & M. A. Horowitz,
“The future of wires,” IEEE
Proc., vol. 89, pp. 490-503,
April 2001.
D. Sylvester et al., “Getting to the
bottom of deep submicron,”
Proc. ICCAD, pp. 203-211, Nov.
1998.
L. Cooke, “Signal integrity effects
in system-on-ship designs – a
designer’s perspective,” in R.
Singh Ed., Signal Integrity
Effects in Custom IC and ASIC
Designs, IEEE Press, 2002
Gate & wire scaling, 1997 NTRS
2
Al 3.0
Cu 1.7
SiO 4.0
Low 2.0
Al & Cu .8 Thick
43 Long
cm
cm
7
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R. B. Wu
Market Impacts on Package
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R. B. Wu
RF Die
Digital Processor Die
Memory Die
Sensor Die
Beyond Moore’s Law
Digital/RF/Memory
Package Integration
New Technologies
System in Package (SiP) and
System on Package (SoP)
Ultra-min. Mobile Computing Platform
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R. B. Wu
RF Die
Digital Processor
Die
Excitation of Edge
Radiation
GND
PWR
Memory
Die Sensor
Die Decoupling
Capacitor
Wire Bond
Signal Line
SSN
Generation SSN Coupling to Signal/Clock Via
SSN Coupling to Power/Ground Via
P/G Via
Signal
Via
• Signal Integrity
• Power Integrity
• Electromagnetic Radiation
• Cross Talk
• Interconnect Coupling
• Substrate Coupling
• Clock Jitter/Skew
• Eye Patterns
• Process Variations
• Yield and Diagnosis
• Mixed Signal Challenges
System Integration Challenges
10
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R. B. Wu
Key Trends in High-Speed Electronics
Year Feature
(nm)
Power
(W)
Vdd
(V)
Current
(A)
Chip Freq
(GHz)
Target Z
(m)
1997 250 70 2.5 28 0.75 4.5
1999 180 90 1.8 50 1.25 1.8
2001 150 110 1.5 73 1.5 1.0
2003 130 130 1.5 87 2.1 0.9
2006 100 70 160 180 1.2 1.1 133 164 3.5 3.9 0.45 0.34
2009 70 50 170 200 0.9 1.0 189 200 6.0 7.6 0.23 0.25
2012 50 36 175 200 0.6 0.9 292 222 10.0 14.9 0.10 0.20
2015 25 200 0.8 250 29.1 0.16
2018 18 200 0.7 286 56.8 0.12
2020 14 200 0.7 286 88.8 0.12
Signal & power integrity is crucial to the success of future
high-speed Electronics!
ITRS – High Performance 1997/2005
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R. B. Wu
Simple Calculation
• Z0_tx-line ~ 50 ohm
• v_tx-line ~ 2 * 1010 cm/sec
• L_tx-line = Z0/v ~ 2.5 nH/cm
• PCB length ~ 10 cm
• f_max ~ 3 GHz
• L ~ 2*3.14* (3 G) * (2.5*10 nH) ~ 500 ohm
• How to reduce it to < 1 mohm?
12
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Technology Scaling
in Transistors
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R. B. Wu
Goal: 1 TIPS by 2010
0.01
0.1
1
10
100
1000
10000
100000
1000000
1970 1980 1990 2000 2010
MIP
S
Pentium® Pro Architecture
Pentium® 4 Architecture
Pentium® Architecture
486 386
286 8086
How do you get there? Courtesy: S. Borkar, Intel 14
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R. B. Wu
GATE
SOURCE
BODY
DRAIN
Xj
Tox D
GATE
SOURCE DRAIN
Leff
BODY
Dimensions scale down by 30%
Doubles transistor density
Oxide thickness scales down
Faster transistor, higher performance
Vdd & Vt scaling Lower active power
Technology has scaled well, will it in the future? Courtesy: S. Borkar, Intel
CMOS Technology Scaling
15
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R. B. Wu
0%
10%
20%
30%
40%
50%
1.5 1 0.7 0.5 0.35 0.25 0.18 0.13 0.09 0.07 0.05
Technology ()
Leakag
e P
ow
er
(% o
f T
ota
l)
Must stop
at 50%
Leakage power limits Vt scaling
A. Grove, IEDM 2002
Courtesy: S. Borkar, Intel
Leakage Power
• Junction leakage
• gate-induced drain leakage
• Subthreshold channel currents
• Gate-insulator tunnel currents
D. J. Frank, Power-constrained CMOS scaling limits,” IBM J. R&D, pp. 235-244, 2000.
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R. B. Wu
1
1.5
2
2.5
3
3.5
1 2 3 4
Die Area, PowerR
ela
tiv
e P
erf
orm
an
ce
Multi Core
Single Core
C1 C2
C3 C4
Cache
• Multi-core, each core Multi-threaded
• Shared cache and front side bus
• Each core has different Vdd & Freq
• Core hopping to spread hot spots
• Lower junction temperature Courtesy: S. Borkar, Intel
Chip Multi-Processing
17
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R. B. Wu
1 TeraByte/s
Power/Freq./BW Tradeoff for Multi-core Processors
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R. B. Wu
Single core processor (45nm)
Multi-core processor (45nm)
Vdd 1.0V 1.0V
I/O pins (total) 1280 (ITRS) 3000 (Estimated)
Operating frequency 7.8GHz 4GHz
Chip-package data rate 7.8 Gb/s 4Gb/s
Bandwidth 125GByte/s 1 TeraByte/s
Power 429.78W 107.39W
Total # of pins on chip 3840 9000 (Est.)
# of pins on package 2480 4500 (Est.)
Comparison btw Single c& Multi-core for 45nm Node
19
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Functioning of Transistors
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R. B. Wu
FN_W
FN_L
FN
_H
2*FN_W
2*FN_W
1.2
*FN
_H
2.4
*FN
_H
Source/Drain
GateDrain/Source
Oxide
OX_T
FN_W
0.5*FN_W
Fin
Transistor from 2D to 3D
NMOS電晶體立體截面圖
https://zh.wikipedia.org/wiki/
鰭狀電晶體結構
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R. B. Wu
Layout of CMOS Inverter
http://www.vlsi-expert.com/2014_11_01_archive.html
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R. B. Wu
Two Types of Transistors
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R. B. Wu
Basic CMOS Output Buffer
※ CMOS output buffer is very common in digital designs. It is
chosen to demonstrate basic principles of buffer modeling.
G.H. Shiue
Basic CMOS Output Buffer
24
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R. B. Wu
])(2[ 2dsdstgsd vvVvKi
)1()( 2
dstgsd vVvKi
Triode region:
Saturation region:
2
ox
ox
WK
t L
2)(1
tgs
ds
d
out
VvKv
i
Z
0typical highveryZout __
CMOS Basic Operation CMOS Basic Operation
2
0
: device mobility (m /V-s)
: oxide permittivity (=3.97 )
: oxide thickness (~5.7 m)
: device width
: gate length
ox
oxt
W
L
25
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R. B. Wu
Vi = Low to High
Vi = High to Low
CMOS Receiver - Operation
26
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R. B. Wu
The Operation of the Basic CMOS Buffer
Pull-
down
Impedance
= inverse of
slope along
I-V curve.
Vi = Low to High
Vi
Vo
Pull-down Operation
27
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R. B. Wu
Pull-up
Impedance =
inverse of slope
along I-V curve
w.r.t. O point
Vi = High to Low
Vi
Vo
Pull-up Operation
28
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R. B. Wu
Capacitance
Load
Effects of Capacitive Load
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Power Delivery Network
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R. B. Wu
Functioning of PDN
D: output node
Ron: on resistance
• Driver is used to charge
& discharge Rx input
capacitance . How
quickly it will be?
• PDN provides the
framework to supply
transistors sufficient
voltage & current to
switch states.
31 (upper) Driver (inverter) connected to a receiver (inverter)
(bottom) Input capacitance of receiver being charged to Vdd
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R. B. Wu
Problems with Power Delivery?
• R&L of wire cause DC drop & time-domain voltage fluctuation, called power supply noise, delta I noise, or Simultaneous switching noise (SSN).
– Decrease in V -> slowdown IC
– Increase in V -> reliability concern.
– Leakage to quiet transistor -> incorrect switching along with crosstalk.
– Degraded waveform -> timing margin error
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R. B. Wu
33
port1
port3
port2
port4
DQ13
Power trace
A Sample PDN for DDR3
Controller
DDR-1
DDR-2 3.3V->1.5V
VRM
GND (TOP)
GND (Bot.)
Top layer Bottom layer
Power traces
Darwin_TFBGA448_DEMO_S4B_L1B_2L
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R. B. Wu
0 1 2 3 4 50.5
1
1.5
2
2.5
VP
Volt
age
(V)
time (ns)
PI-SI cosim
no coupling
Transient Simulation (pull-down)
34
No decap.
Max. voltage diff. is 27mV.
Small ripple is caused by VP .
If p-p diff. of VP is larger,
ripple becomes larger.
Driver
0-1.5V
Ron=36Ω
tr=125ps
Vdd=1.5V
RL=70Ω
CPW couple line
C=1.23pF
Power trace
DQ13
0 1 2 3 4 5-0.2
0
0.2
0.4
0.6
0.8
1
1.2
VP
Volt
age
(V)
time (ns)
PI-SI cosim
no coupling
1 1.5 2 2.5 3-0.04
-0.02
0
0.02
0.04
Pull-down
Volt
age
(V)
time (ns)
pi-si cosim
no coupling27mV
VP
VL
1.8V 1.7ns
LV
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R. B. Wu
It might Cause Closed Eye
35
Logic 1 becomes very small when
VP is small. Driver
0-1.5V
Ron=36Ω
tr=125ps
Vdd=1.5V
RL=70Ω
CPW couple line
C=1.23pF
Power trace
DQ13
VP
VL
0 1 2 3 4 50
0.5
1
1.5
VL
Vo
ltag
e (V
)
time (ns)
y101-y100
y001
0 1 2 3 4 50
0.5
1
1.5
2
2.5
VP of y101
Volt
age
(V)
time (ns)
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R. B. Wu
RL
PTL_Ctrl Pwr_CTRL
VSSQ
CTRL_NTL_DQN
Data_OUTN
Data_IN_N
VsupZsig
ZCTRL
RL
CTRL_1TL_DQ1 Data_
OUT1Data_IN_1 Zsig
Rs
Ron
It might Cause Detrimental Voltage
36
32 DQ lines.
No coupling: no DQ line
coupled with power trace.
PI-SI cosim: only one DQ line
coupled with power trace.
VP VL
_ sup ( )
on LCTRL
Pwr CTRLon L
R RZ
N NV VR R
N N
0 1 2 3 4 5-40
-20
0
20
40
VP
Vo
ltag
e (V
)
time (ns)
PI-SI cosim
no coupling
0 1 2 3 4 5-1.5
-1
-0.5
0
0.5
1
VP
Vo
ltag
e (V
)
time (ns)
PI-SI cosim
no coupling
LV
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R. B. Wu
Reliability Wall
50MHz
Increase
In FMAX
+/- 100mV
+/- 50mV
1.40 1.45 1.50 1.55 1.60 1.65 1.70 1.75 1.80
825
785
745
705
665
625
FMAX (MHz)
VCC (V) Courtesy: Intel
Importance of Power Delivery
37
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R. B. Wu
High-f Caps
Mid-f Caps
Motherboard
VRM
Power Delivery Network
. VRM
. Interconnects
. DeCap’s on PCB & package 38
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R. B. Wu
Noise Signature
A. Muhtaroglu, G. Taylor, and T. Rahal-Arabi, “On-die droop detector for analog sensing
of power supply noise,” IEEE J-SSC, pp. 651–660, Apr. 2004, © 2004 IEEE.
Noise Signature
39
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Power Supply Noise
40
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R. B. Wu
Signal Wires
Active Device (IC)
Core Circuits
(Comm. within IC) I/O Circuits
(Comm. outside IC)
Core and I/O Circuits
Current
Vdd
Gnd
Core and I/O Circuits
Core: transistors within
an IC and communicate with each other.
I/O: need communicate with other ICs though package
and motherboard. 41
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R. B. Wu
42
Vo
0R
Linear Behavior Model -1
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R. B. Wu
Linear-Linear Model -2
Better if run in freq domain rather than time domain
model
interpretation
43
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R. B. Wu
Core Circuits Switching
(1 )( )
( )( 1 )
(1 )
( )
r
r
t s
dd rL
t s
dd r
V e t LV s
s R L s RC
V e t L
s s R L
44
PMOS
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R. B. Wu
( ) ( )( ) ( ) ( )
0( ) ( ) (1 ) ( )
L
ddr
r dd dd r
r r
dd r
di t di tV t L L Ri t v t
dt dt
V tt t t t
tV t V u t V u t tt t
V t t
45
2
2
1
,max
1( ) ( ) (1 )
1 1( ) (1 )
( ) (1 ) ( ) Shift of
( )( ) ; ( ) (1 )
r
r
r
stdd
r
stdd
r
Rt
dd Lr
r
Rt
dd LL L L r
r
VL sI s RI s e
t s
VI s e
t s sL R
V Li t t e u t t
R t R
di t VV t L V V t L e
dt R t
L
L
Voltage Drop due to SSN
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R. B. Wu
I/O Circuits Switching
max. voltage drop:
or
)1(max
ro t
L
Z
ro
ddL e
tZ
VLvV
0
; if ddr
o r
V Lv L t
Z t Z
46
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R. B. Wu
Delay Due to SSN
• Voltage at input end of tx-line
2 2
2
(1.12) 1
(1.13) 1
1( ) ( )
1
o
o or
o
Zt
dd dd Lchip r
r r o
Z Zt t
dd L Lchip dd r
r o
Zt
dd L
r o o o
ddr
r o o
V t L VV e t t
t t Z
L VV V e e t t
t Z
V L LI t t e u t
t Z Z Z
V Lt t
t Z Z
2
or
Zt t
Lr
o
Le u t t
Z
47
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R. B. Wu
CORE CIRCUITS I/O CIRCUITS
Transient current through inductors causes voltage fluctuations across Vdd
and Gnd terminals of the circuit
dt
dILV
Power Supply Noise
48
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R. B. Wu
Jitter caused by SSN for I/O
Uncertainty in Delay due to SSN causing Jitter
Varying voltage
droop on power
supply due
to SSN
time
Output driver waveform
Vdd
Jitter caused by SSN for I/O
49
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Target Impedance
50
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R. B. Wu
Target Impedance
• Target impedance states that voltage to current ratio has to equal the impedance in the network. If exceeds it at any freq., resultant power supply noise will exceeds 5% of Vdd
51
p.s. allowed
transient
%
50%
T
dd
Max
VZ
I
V Ripple
I
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R. B. Wu
Courtesy: Larry Smith (SUN)
Power Distribution Historical Trends
Target impedance for intel microprocessor decreases
500X in 1991-2002.
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R. B. Wu
Realistic Target Impedance
• Spectrum of pulse is
frequency dependent, with
higher freq. spectrum smaller,
target impedance can be
frequency dependent too.
53
0.1 1 10 100 1000Frequency(MHz)
0.001
0.01
0.1
1
Z r
es
po
nse
(Oh
ms)
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R. B. Wu
Resonance of
Decoupling
Capacitor
@ 0.5MHz
Anti-resonance
Circuit of PDN & Freq. Response
2
3
320
100
1
800
dd
s
s
chip
V V
R m
L pH
C F
ESL nH
C nF
target5%
10 10I A Z m
Max. imped. allowed
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R. B. Wu
Voltage assuming 3m in impedance network
Idea: Switching circuit is represented using a time-dep.
resistor and simulate voltage across it.
Simulation of Power Supply Noise
97 197
rise time 10
only 3 in PDN
@97 , 20
@197 , 10
10
DC
DC
R m m
ns
m
m I A
m I A
I A
DC
tot
20A 10A under 2V
2 / 20 2 /10 100 200
I V
R m m
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R. B. Wu
(b) 1us current period
(settled after 50ns)
(c) 80ns current period
(~ 13MHz)
(b)
97 m to
197 m
(c)
Voltage
assuming 3m
in impedance network
+5%
-5%
+5%
-5%
Two Current Signatures
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R. B. Wu
Have you Learned?
• What is PDN?
• Why and how the PDN will cause noise?
• What is power supply noise?
• Why it is also called inductive noise, SSN noise?
• What are key parameters for inductive noise?
• What is target impedance? Why?
• How to simulate and assure it meets target
impedance?
• What is noise signature? How to simulate it?
57
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R. B. Wu
Summary
• Power delivery noise is a challenge nowadays.
• The challenge will increase since:
– Device scale, more transistors, & smaller system
– Power & current increase, but voltage decreases
– Need clean power to transistor circuits, with Gbps propagating through package & boards
– EMI levels kept low to manage coupling & crosstalk
• Leakage power problem leads to multi-core processors
• Core & I/O circuit analysis is presented to estimate power delivery noise voltage and its effects on delay and jitter.
• Target impedance is an important parameter for power delivery design
• Power noise signature can depict PI in time domain. 58