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International Journal of Applied Engineering Research ISSN 0973-4562 Volume 12, Number 12 (2017) pp. 3243-3247
© Research India Publications. http://www.ripublication.com
3243
Antenna Array with Low Mutual Coupling for MIMO-LTE Applications
Eduardo Rodríguez Araque1, Ezdeen Elghannai2, Roberto G. Rojas3 and Roberto Bustamante4
1Foundation Universitary Cafam (Unicafam), Bogotá, Colombia. 2Ohio State University, USA, 3MIT Lincoln Laboratory, USA, 4University of Los Andes, Bogotá, Colombia.
1ORCID: 0000-0003-0229-7920
Abstract
In this work we present a compact MIMO array platform that
operates in the 2.6 GHz for Long Term Evolution (LTE) band
and wireless communication systems. The array consists of
four compact patch antennas on a dielectric substrate with total
dimensions of 125 mm 62.5 mm 1.27 mm. Modifications
on the ground plane along with systematic placement and
orientation of each antenna on top of the substrate plays a key
role in reducing the mutual coupling which normally degrades
the MIMO array performance. The performance of this
designed MIMO array is assessed through simulations and
measurements of the scattering parameters, radiation patterns,
and correlation coefficients, including an evaluation of the
capacity in indoor and outdoor-to-indoor scenarios with
outstanding results.
Keywords: Antenna array, Capacity, Characteristic Modes,
Correlation, Diversity, Multiple-Input-Multiple-Output
(MIMO) systems, mutual coupling
INTRODUCTION
The operation of MIMO array systems is based on a technique
that allows us to increase the data rate and link reliability when
operating in rich scattering environments. This technique
normally generates low-correlation parallel sub-channels
between elements of the array, thus incrementing the system
capacity by several orders of magnitude [1].
An important factor that has a deleterious effect on the MIMO
system performance is the mutual coupling between antennas.
A high level of mutual coupling can increase the correlation
between the signals received by each antenna, which in turn,
reduces the number of independent parallel sub-channels [2].
There are different techniques to reduce the mutual coupling
between the elements of an array; one way is to increase the
spacing between antenna elements of the array. However, if the
antenna array is built within small mobile phones, expanding
the spacing is not realistic.
Several antenna designs have been proposed to reduce the
mutual coupling of MIMO arrays in small mobile phones.
Corrugated ground plane techniques are presented in [3-4] to
achieve high isolation. A T-shaped ground plane slot is
implemented to reduce the mutual coupling between antennas
[5]. In [6], T-shaped and dual inverted are inserted to reduce
the mutual coupling. Additionally, neutralization techniques
are also used to increase the port-to-port isolation between two
closely placed antennas [7].
In this work, we propose a MIMO array designed to operate at
2.6 GHz (4G-LTE) band. The antenna array consists of four
compact patch antennas on a PCB/dielectric substrate.
Modification of the ground plane (GND) with corrugated slots
in addition to a systematic placement and orientation of each
antenna on top of the PCB plays a key role to increase the
isolation; therefore, reducing the correlation between antennas.
The design of the antenna elements, modifications of the GND,
placement, and orientation of each antenna on the array was
done based on the insights provided by the method of
Characteristic Modes.
The Method of Characteristic Modes (CMs) is a modal analysis
scheme that provides physical insight into the potential
resonant characteristic of a structure by finding and rigorously
examining the natural current modes of the structure [8-9]. We
used the original CMs [9] to design the antenna elements as
well as to study the currents induced on the ground plane of the
MIMO array. Another version of this method is the Network
Characteristic Mode (NCM) technique, in this application; the
network is formed by the 4 input ports of the antenna elements.
DESIGN OF MIMO ARRAY
The goal is to design and build a four-element array within a
compact mobile chassis and with high isolation between the
antennas. The first step was the initial design of a single antenna
that operates at 2.6 GHz. Thanks to miniaturization techniques,
we were able to design an electrically small antenna by properly
inserting slots as depicted in Fig. 1. Note that this antenna has
a radiation efficiency of 63 % after miniaturization.
International Journal of Applied Engineering Research ISSN 0973-4562 Volume 12, Number 12 (2017) pp. 3243-3247
© Research India Publications. http://www.ripublication.com
3244
Figure 1: Compact patch antenna at 2.6 GHz. (a) Geometry.
(b) Return loss. (c) Radiation Pattern in E-plane. (d) Radiation
pattern in H-plane. The maximum measured gain is 2.79 dBi.
The next step is to place four antennas equal to the one in Fig.
1(a) on the substrate and try to achieve very low mutual
coupling between them.
A. Ground Plane Modifications
We start with a baseline structure; namely, with four equally
spaced antennas and with the same orientation as shown in Fig.
2(a). The initial GND is a solid metal sheet. The first step to
reduce mutual coupling between the array elements is to
introduce slots in the GND. These slots can reduce surface
waves effects in the substrate. The careful design of the slots
allows us to modify the GND taking into considering the
position of each slot as well as the spacing between antennas.
The total current distribution on the original GND (baseline
structure) at 2.6 GHz can be seen in Fig 2(b). Initially, straight
slots were introduced on the GND resulting in a reduction of
the mutual coupling. Further reduction was obtained by
modifying the edges of the slots so they are corrugated as
depicted in Fig. 2(c). The total current of the corrugated GND
is shown in Fig. 2(d). It can be observed how the total current
between antennas decreases substantially when the corrugated
slots are introduced. This means that there is less interaction
between the antennas and therefore a reduction in mutual
coupling between them.
B. The Placement and Orientation of the Antennas
Additional modifications are necessary to obtain a better
performance, i.e. greater reduction in the correlation. The first
modification is to change the location of each antenna on top of
the substrate. Initially, each antenna is centered in its
corresponding ground plane bounded by slots and all are
oriented in the same direction (see fig. 2(d)), then; further
modifications related to the antenna rotations are performed.
We observed that rotating each antenna helps to improve the
polarization diversity so that the correlation is reduced.
One way to achieve the optimum orientation of each antenna in
the array is by using the physical insight provided by the
method of NCM. The NCM eigenvalue spectrum for the four
antennas of the array with corrugated slots in the GND and each
antenna located in the center of the corresponding ground plane
and with the same orientation can be seen in Fig. 3(a). It can be
seen that the behavior of the modes corresponding to antennas
#1 and #2 show similar behavior and resonate near 2.6 GHz;
however, the resonance frequencies of the dominant modes for
the other two antennas are shifted. We see the magnitude of S11
and S22 resonate near 2.6 GHz, while S33 and S44 are shifted.
After rotating the antennas, the results of these modifications
can be seen in Fig. 3(b) and Fig. 3(d). The latter shows that all
antennas resonate near 2.6 GHz due to the weaker mutual
coupling between them. Note that a more detailed CM analysis
was performed to confirm these results; however, we can’t
present these additional details due to space constraints.
Fig. 4 shows the final arrangement of the four antennas on top
of the dielectric and the geometry of the ground plane.
RESULTS AND DISCUSSION
The results from measurements and simulations of the
proposed array are presented for S-parameters, mutual
coupling, enveloped correlation coefficients, radiation patterns,
and the simulated MIMO ch annel capacity at a frequency of
2.6 GHz.
Figure 2: Design Process. (a) Baseline structure with 4-
element antennas. (b) Total current distribution at 2.6 GHz of
baseline ground plane (mA/m). (c) Modified GND with
corrugated edge slots (5 mm x 2.5 mm). (d) Total current
distribution at 2.6 GHz of modified GND (mA/m).
International Journal of Applied Engineering Research ISSN 0973-4562 Volume 12, Number 12 (2017) pp. 3243-3247
© Research India Publications. http://www.ripublication.com
3245
Figure 3: NCM eigenvalue spectrum of the dominant mode
and Return Loss (RL) for each antenna at 2.6 GHz. (a)
Eigenvalue before rotation. (b) Eigenvalue after rotation. (c)
Simulated RL of each antenna before rotation. (d) After
rotations (see Fig. 4(b)).
Figure 4. The designed MIMO array with total dimensions of
125 mm 62.5 mm 1.27 mm. (a) Four small patch antennas
on top of substrate (r=4.5, tan=0.002) (b) Modified Ground
Plane (GND), with corrugated slots.
A. S-Parameters and Mutual Coupling
Fig. 5 shows the results of the simulated and measured S-
parameters (respect to 50-ohms reference) for all antennas on
the substrate. The return loss values (Sii) show an acceptable
agreement between simulated and measured results. The
measured mutual coupling (Sij, ij) between antennas remains
below -28.42 dB at 2.6 GHz as shown in Fig. 5(c). We show an
excellent agreement with the simulated results where the
mutual coupling is found to be below -25.4 dB at 2.6 GHz.
B. Enveloped Correlation Coefficients
An important parameter that provides very significant
information about the performance of the array for MIMO
systems is the correlation. This correlation between signals
received by the antennas of the array can be computed through
the S-parameters for a lossless MIMO antenna [10-12]. The
results of the coefficients calculated through the measured S-
parameters are plotted in Fig. 5(d).
The results are less than 0.000027 at 2.6 GHz; these very low
values indicate that more isolated parallel sub-channels can
exist with the proposed MIMO array. Fig. 5(b) shows the
coefficients calculated through the simulated S-parameters. It
can be noticed that all the values are still very small. The results
for the coefficients of the baseline array are shown in fig. 5(f).
It shows high correlation with regard to the results of the
proposed array (see Fig. 5d), implying that this baseline array
has poor MIMO performance.
Figure 5: S-parameters and the correlation coefficients of the
MIMO array, and baseline array. (a) Simulated S-parameters.
(b) Correlation using simulated S-parameters. (c) Measured S-
parameters. (d) Correlation using measured S-parameters. (e)
Simulated S-Parameters of the baseline array, the isolation of
this array is 13.79 dB, and all antennas are not well matched at
2.6 GHz (f) Correlation of the baseline array. The S-parameters
are measured while all other antennas are terminated in 50-ohm
loads.
C. Radiation Patterns and Pattern Diversity
The simulated and measured radiation patterns at 2.6 GHz of
each antenna of the proposed array are plotted in the Fig. 6. We
can see that each antenna shows a different radiation pattern
(pattern diversity); this favorable property helps reduce the
correlation because the received multipath distribution in each
antenna will be different. Furthermore, the simulated and
measured radiation patterns show good agreement with a
maximum achieved gain of 3.15 dBi.
(a) (b)
(c) (d)
2.55 2.6 2.650
0.05
0.1
Frequency (GHz)
Ma
gn
itu
de
r12
r13
r14
r23
r24
(e) (f)
2.55 2.6 2.650
1
2
3
4
5
6
x 10−4
Frequency (GHz)
Mag
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ud
e
r12
r13
r14
r23
r24
International Journal of Applied Engineering Research ISSN 0973-4562 Volume 12, Number 12 (2017) pp. 3243-3247
© Research India Publications. http://www.ripublication.com
3246
D. MIMO Channel Capacity Evaluation
The MIMO channel capacity is an important performance
metric for a wireless communication system. The capacity can
be calculated through the matrix of the MIMO channel (H) [2].
Here, the H matrix for the propagation environment depicted in
fig. 7 was obtained through simulations based a 3D GO/UTD
ray-tracing model [13]. Additionally, to obtain an accurate
interpretation of the capacity, the path loss and receive SNR
effects should be carefully removed [14].
Figure 6. Simulated ( ), and measured ( ) 2-D radiation
patterns. (a) Antenna #1. (b) Antenna #2. (c) Antenna #3. (d)
Antenna #4. See Fig. 4(b). The measurements was performed
by exciting one antenna while the others antennas were
terminated by 50-ohm loads.
Simulated capacity for a 4×4 MIMO system in a specific
propagation environment at a frequency of 2.6 GHz are
presented for two locations of the receiving and transmitting
array as shown in fig 7. We present results for three receiving
arrays: 1) designed MIMO array, 2) baseline array, and 3) four
parallel dipole antenna array with spacing of /2 between them
and without mutual coupling. This latter array together with the
transmitting array form a MIMO system and are used as a
reference for evaluating the MIMO capacity, since these two
arrays do not take into account mutual coupling effects.
Fig. 8(a) shows the capacity calculated for an indoor scenario
for two cases: line of sight, and not line of sight. As expected,
we show that none of the evaluated antenna arrays (proposed
MIMO and baseline arrays) can achieve the performance of the
reference MIMO system due to the presence of mutual
coupling. However, the designed MIMO array presents better
performance than the baseline array due to the high isolation
between its elements.
Figure 7: Layout of propagation environment of the floor #1.
The positions of the transmitting, and receiving arrays are
shown above. The Tx. array consists of four vertical λ/2-
dipoles with a spacing of /2 between them.
In Figs. 8(b-c) the designed MIMO array performance presents
two different behaviors that can be attributed to the multipath
angular distribution arriving at the receiver array. Fig. 8(b)
shows its capacity curve is the lowest when the receiver is
located in a narrow hallway where the various multipath
components arriving at the receiver are concentrated in certain
directions, thus limiting the performance the MIMO system.
Note that the hallway behaves as a waveguide for multipath
propagation [15]. Fig. 8(c) shows its capacity curve is almost
equal to that of the dipole array which has not mutual coupling.
In this case, the receiver array is located in a large room that
allows multipath components to arrive in many directions (high
angular dispersion). Large angular dispersion is one of the
fundamental conditions for the best performance of a MIMO
array [12].
The outstanding results shown here validate the fact that
reducing the mutual coupling greatly increases the performance
of a MIMO system.
(a)
(b)
(d)
(c)
International Journal of Applied Engineering Research ISSN 0973-4562 Volume 12, Number 12 (2017) pp. 3243-3247
© Research India Publications. http://www.ripublication.com
3247
CONCLUSION
In this work, a four-element antenna array with compact
miniaturized patch antennas for MIMO-LTE systems at 2.6
GHz is presented. With the modification of the ground plane
with corrugated slots along with an optimized location and
orientation of the each antenna elements based on the insight
provided by the theory of Characteristic Modes, it was possible
to design and fabricate a MIMO array with very low mutual
coupling and extremely low correlation coefficients.
Furthermore, the radiation characteristics observed in the
proposed array have the ability to overcome propagation
problems of the channel such as multipath fading, line of light
path, and other issues due to polarization and pattern diversity.
Figure 8: Capacity against the SNR. (a) Transmitter at position
#2, and Receiver array at position #1 (LOS), and position #2
(NLOS). (b) Receiver array at position #1 and Tx. at position
#1. (c) Receiver array at position #2 and Tx. at position #1.
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